Power converter having a synchronous rectifier

ABSTRACT

In an aspect, the present invention provides a high frequency switching power converter. The high frequency switching power converter may include a plurality of soft-switchable power cells flexibly connected to receive an input signal in series and provide an output. The high frequency switching power converter may further include a controller for configuring the flexible connection and for controlling the power cells to receive the input signal. In an embodiment, each of the plurality of power cells may be separately controllable by the controller. Further, a portion of the plurality of power cells may be arranged with parallel outputs. Additionally, at least one of the plurality of cells may include one or more switched capacitors. In another embodiment, the at least one of the plurality of cells may include at least one switched capacitor and a DC/DC regulating converter.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. Ser. No. 13/213,031, filedAug. 18, 2011, which claims the benefit of the following provisionalapplications: U.S. Ser. No. 61/374,993 filed Aug. 18, 2010; U.S. Ser.No. 61/374,998 filed Aug. 18, 2010; and U.S. Ser. No. 61/392,329 filedOct. 12, 2010. Each of the above-identified applications is herebyincorporated by reference in its entirety.

BACKGROUND OF THE INVENTION

1. Field:

The methods and systems described herein relate to very high frequencypower conversion technology, techniques, methods, applications, andsystems.

2. Description of the Related Art:

Increasing the switching frequency of a switched-mode power supply(SMPS) is a goal that is widely sought after as a means to increasepower density and improve transient performance. However, increasingswitching frequency using conventional power converter topologies(boost, buck, flyback, etc.) results with significantly degradedefficiency. Additionally, as switching frequency is increased, powerdensity only increases until an optimal switching frequency is reached,at which point power density begins to decrease again. Therefore,conventional solutions appear to be lacking to satisfy demand.

SUMMARY OF THE INVENTION

The methods and systems described herein may comprise a next-generationvery high frequency (VHF, 30-300 MHz) power supply architecture usingchip-scale components. Fundamental technology and methods of VHFconversion and exemplary benefits for solid-state lighting applicationsand the like are outlined herein in light of several enhancementsenabled by the methods and systems described herein. Furtherapplications of the core VHF converter architecture, both AC-DC andDC-DC are enumerated in the figures and associated descriptions.Together these elements provide both a description of the basicinnovations and methods and a range of useful and beneficialapplications for those innovations.

In the case of line-connected LED drivers, which are AC-DC convertersfor general illumination applications, the benefits are severalincluding a greater than 10-fold reduction in volume, much lower cost,higher reliability, a high degree of integration, high efficiency andvery fast transient response. Taken together these characteristics formthe basis for a useful array of LED driver systems suitable for bothretrofit lamps, such as A19, MR16, GU10, and various PAR forms, as wellas in solid-state luminaires. However, applications of the inventivevery high frequency chip-scale power supply architecture are not limitedto LED and/or solid state drivers. This technology may be used in anyapplication that can benefit from the several benefits described herein.

The unique characteristics of the VHF power supply architecturedescribed herein enables power converters with very high power density,high performance, and high transient response while utilizing very fewcomponents. This enables applications in many spaces, such as SolidState Lighting and portable mobile devices, where size and cost are ofkey concern, and military and industrial applications where the highestpower densities and improved reliability due to simpler and fewercomponents are of interest. One exemplary application is radar,particularly air-intercept radar on fighter jets, where size, weight,and transient performance are key attributes. Present power convertersystems require large and heavy capacitor banks to sustain transientsdemanded by the radar under transmit. By utilizing the inventiondescribed herein, these capacitors no longer need to be sized bytransient considerations, rather ripple alone. This allows a dramaticreduction in bulk energy storage in combination with the reduction inthe main power stage. This set of features will offer a clear advantagein such high-performance military applications.

In the retrofit lamp space the needs are several: foremost is therequirement for low cost, nearly as important is small size, whilehigh-performance (efficiency), high-reliability, and a full range offunctionality are all of keen interest depending on the particular lamptype and intended target market. In each case, the existing powerconverter technology falls short of desired characteristics necessary topropel SSL lamps to commercial success. The inventive technologydescribed herein in this area addresses each of these shortfalls andoffers a compelling package to a lamp maker.

In an aspect, the present invention provides a high frequency switchingpower converter. The high frequency switching power converter mayinclude a plurality of soft-switchable power cells flexibly connected toreceive an input signal in series and provide an output. The highfrequency switching power converter may further include a controller forconfiguring the flexible connection and for controlling the power cellsto receive the input signal. In an embodiment, each of the plurality ofpower cells may be separately controllable by the controller. Further, aportion of the plurality of power cells may be arranged with paralleloutputs. Additionally, at least one of the plurality of cells mayinclude one or more switched capacitors. In another embodiment, the atleast one of the plurality of cells may include at least one switchedcapacitor and a DC/DC regulating converter.

The high frequency switching power converter may also include an outputstage for receiving outputs from the portion of the plurality of powercells to provide a combined output and for delivering the combinedoutput to a load. The output stage may include at least one transformerwith multiple primary windings. Further, each of the multiple primarywindings may receive an output from one of the plurality of power cells.The output stage may further include a plurality of capacitors, an inputof each of which may be connected to an output from one of the pluralityof cells. Further, an output of each of the plurality of capacitors maybe connected in parallel for providing the combined output. In anembodiment, the output stage may facilitate configuring a paralleloutput combination of the plurality of power cells. The DC/DC regulatingconverter may be disposed between the at least one switched capacitorand the output stage.

In an embodiment, the high frequency switching power converter mayinclude a plurality of sets of stacked cells each set providing at leastone output. Further, a portion of the plurality of sets of stacked cellsmay be configured to provide parallel outputs. The high frequencyswitching power converter may further include PCB etched inductorsand/or transformers with or without magnetic core material, varactorcontrolled network tuning, resonant switching, and the like. In anotherembodiment, the high frequency switching power converter may be adaptedfor use with a laptop, may be integrated into a display screen module,may be integrated into an AC line power cord assembly, may be adaptedfor use with a mobile phone, may be integrated into a wireless basestation, may be integrated into an electrical vehicle, may be adaptedfor use with airborne radar, and the like.

In another aspect, the present invention provides a stacked cellswitching power converter. The stacked cell switching power convertermay include a plurality of stacked power cells flexibly connected toreceive a DC input signal in series and may provide a DC output. Thestacked cell switching power converter may also include a controller forconfiguring the flexible connection. The controller may control theplurality of stacked power cells to receive the DC input signal, and mayfacilitate resonant switching. Further, the stacked cell switching powerconverter may include an output stage for combining an output from eachof a portion of the plurality of stacked power cells to deliver acombined DC output to a load.

In an embodiment, the stacked cell switching power converter may includePCB etched inductors and/or transformers with or without magnetic corematerial, varactor controlled network tuning, resonant switching, andthe like. In another embodiment, the stacked cell switching powerconverter may be adapted for use with a laptop, may be integrated into adisplay screen module, may be integrated into an AC line power cordassembly, may be adapted for use with a mobile phone, may be integratedinto a wireless base station, may be integrated into an electricalvehicle, may be adapted for use with airborne radar, and the like.

In yet another aspect, the present invention provides a stacked cellsoft-switchable power converter. The stacked cell soft-switchable powerconverter may include a plurality of stacked power cells flexiblyconnected to receive an input signal and provide an output. Further, thestacked cell soft-switchable power converter may include a controllerfor configuring the flexible connection. The controller may control theplurality of stacked power cells to receive the input signal, and mayfacilitate power cell soft switching. The stacked cell soft-switchablepower converter may also include an output stage for receiving an outputfrom each of a portion of the plurality of stacked power cells and fordelivering a combined output to a load.

In an embodiment, the stacked cell soft-switchable power converter mayinclude PCB etched inductors and/or transformers with or withoutmagnetic core material, varactor controlled network tuning, resonantswitching, and the like. In another embodiment, the stacked cellsoft-switchable power converter may be adapted for use with a laptop,may be integrated into a display screen module, may be integrated intoan AC line power cord assembly, may be adapted for use with a mobilephone, may be integrated into a wireless base station, may be integratedinto an electrical vehicle, may be adapted for use with airborne radar,and the like.

In still another aspect, the present invention provides a silicon-basedstacked-cell switching power converter. The silicon-based stacked-cellswitching power converter may include a plurality of silicon power cellsconfigured in a series stack to receive an input signal with a peakamplitude greater than 50V and to provide an output from each of theplurality of silicon power cells. The silicon-based stacked-cellswitching power converter may further include a controller forcontrolling the plurality of silicon power cells to receive the inputsignal. The controller may facilitate switching the silicon-basedstacked-cell switching power converter at a frequency in excess of 5MHz. In addition, the silicon-based stacked-cell switching powerconverter may include an output stage for receiving an output from aportion of the plurality of silicon power cells and for delivering acombined output to a load.

In an embodiment, the silicon-based stacked-cell switching powerconverter may include PCB etched inductors and/or transformers with orwithout magnetic core material, varactor controlled network tuning,resonant switching, and the like. In another embodiment, thesilicon-based stacked-cell switching power converter may be adapted foruse with a laptop, may be integrated into a display screen module, maybe integrated into an AC line power cord assembly, may be adapted foruse with a mobile phone, may be integrated into a wireless base station,may be integrated into an electrical vehicle, may be adapted for usewith airborne radar, and the like.

In yet another aspect, the present invention provides a low powerdensity stacked-cell switching power converter. The low power densitystacked-cell switching power converter may include a plurality of powercells configured to receive an input signal with a peak amplitudegreater than 50V in series and to provide an output. Further, the lowpower density stacked-cell switching power converter may include acontroller for configuring the plurality of power cells to receive theinput signal. The controller may facilitate switching the low powerdensity stacked-cell switching power converter at a frequency in excessof 5 MHz. The low power density stacked-cell switching power convertermay also include an output stage for receiving an output from a portionof the plurality of power cells and for delivering a combined output toa load. In an embodiment, the low power density stacked-cell switchingpower converter may provide power density that may be lower than powerdensity provided by a single cell power converter providing asubstantially identical function.

In an embodiment, the low power density stacked-cell switching powerconverter may include PCB etched inductors and/or transformers with orwithout magnetic core material, varactor controlled network tuning,resonant switching, and the like. In another embodiment, the low powerdensity stacked-cell switching power converter may be adapted for usewith a laptop, may be integrated into a display screen module, may beintegrated into an AC line power cord assembly, may be adapted for usewith a mobile phone, may be integrated into a wireless base station, maybe integrated into an electrical vehicle, may be adapted for use withairborne radar, and the like.

In still another aspect, the present invention provides astacked-silicon cell switching power converter. The stacked-silicon cellswitching power converter may include a plurality of silicon powerconverter cells configured in a series stack to receive an input signalwith a peak amplitude greater than 50V and to provide a plurality ofoutputs. Further, the stacked-silicon cell switching power converter mayinclude a controller for controlling the plurality of silicon powerconverter cells to ensure that no silicon power converter cell receivesan input signal in excess of 60V. The controller may facilitateswitching the stacked-silicon cell switching power converter at afrequency in excess of 5 MHz. In addition, the stacked-silicon cellswitching power converter may include an output stage for combining anoutput from each of a portion of the plurality of silicon powerconverter cells to deliver a combined output to a load.

In an embodiment, the stacked-silicon cell switching power converter mayinclude PCB etched inductors and/or transformers with or withoutmagnetic core material, varactor controlled network tuning, resonantswitching, and the like. In another embodiment, the stacked-silicon cellswitching power converter may be adapted for use with a laptop, may beintegrated into a display screen module, may be integrated into an ACline power cord assembly, may be adapted for use with a mobile phone,may be integrated into a wireless base station, may be integrated intoan electrical vehicle, may be adapted for use with airborne radar, andthe like.

In yet another aspect, the present invention provides a stacked-siliconcell switching power converter. The stacked-silicon cell switching powerconverter may include a plurality of silicon power converter cellsconfigured in a series stack to receive an input signal with a peakamplitude greater than 50V and to provide a plurality of outputs. Thestacked-silicon cell switching power converter may further include acontroller for controlling the plurality of silicon power convertercells to ensure that no silicon power converter cell receives an inputsignal less than 20V nor in excess of 60V. The controller may facilitateswitching the stacked-silicon cell switching power converter at afrequency in excess of 5 MHz. The stacked-silicon cell switching powerconverter may also include an output stage for combining an output fromeach of a portion of the plurality of silicon power converter cells todeliver a combined output to a load.

In an embodiment, the stacked-silicon cell switching power converter mayinclude PCB etched inductors and/or transformers with or withoutmagnetic core material, varactor controlled network tuning, resonantswitching, and the like. In another embodiment, the stacked-silicon cellswitching power converter may be adapted for use with a laptop, may beintegrated into a display screen module, may be integrated into an ACline power cord assembly, may be adapted for use with a mobile phone,may be integrated into a wireless base station, may be integrated intoan electrical vehicle, may be adapted for use with airborne radar, andthe like.

In still another aspect, the present invention provides a VHF powerconverter. The VHF power converter may include a switched capacitorstage. The switched capacitor stage may include a plurality of switchedcapacitors for dividing the input voltage among the plurality ofcapacitors. The VHF power converter may further include a bypass switch.The bypass switch may select between the input voltage and an output ofthe switched capacitor stage. Further, a control of the bypass switchmay be based on the input voltage. The VHF power converter may alsoinclude a VHF regulating stage for converting an input voltage to anoutput voltage. The switched capacitor stage may be followed by theby-pass switch that may be further connected to the VHF regulatingstage.

In an embodiment, the VHF power converter may include PCB etchedinductors and/or transformers with or without magnetic core material,varactor controlled network tuning, resonant switching, and the like. Inanother embodiment, the VHF power converter may be adapted for use witha laptop, may be integrated into a display screen module, may beintegrated into an AC line power cord assembly, may be adapted for usewith a mobile phone, may be integrated into a wireless base station, maybe integrated into an electrical vehicle, may be adapted for use withairborne radar, and the like.

In another aspect, the present invention provides a method ofcontrolling average power delivered from a VHF power converter to anauxiliary output. The method may include rectifying AC power that may begenerated from an inverter of the VHF power converter and providing itto an auxiliary power port in a first phase. The auxiliary power portmay be used to supply the power required to drive gates of one or morepowered devices. In an embodiment, the powered device may be anLED-based lighting unit. The auxiliary power port may also be used toprovide power to a portion of the VHF power converter.

The method may further include generating AC power from the auxiliarypower port and providing it to the VHF power converter in a secondphase. Switching between generating auxiliary power in the first phaseto generating AC power in the second phase may be controlled tofacilitate controlling an average power delivered from the VHF powerconverter. In an embodiment, the method may further include controllingthe auxiliary rectifier in an auxiliary power control loop that may beindependent of a control loop of the VHF power converter for providingpower to a load. In embodiments, the auxiliary power control loop may bea feed forward control loop.

In another aspect, the present invention provides a method. The methodmay include receiving a varying input voltage signal to be applied to aplurality of series stacked high frequency power converter cells. Theplurality of series stacked high frequency power converter cells forproducing an output from the varying input voltage signal. In anembodiment, the varying input voltage signal may be an AC line signal.Further, the output may be a DC voltage, a fixed current, and the like.In an embodiment, individual cells of the plurality of series stackedhigh frequency power converter cells may be activated at differentdetermined amplitudes as the amplitude of the varying input voltagesignal varies. The individual cells of the plurality of series stackedhigh frequency power converter cells may be deactivated at differentamplitudes as the determined amplitude of the varying input voltagesignal decreases. Further, the individual cells of the plurality ofseries stacked high frequency power converter cells may be bypassed atdifferent determined amplitudes as the determined amplitude of thevarying input voltage signal decreases.

In another embodiment, each of the plurality of series stacked highfrequency power converter cells may be separately controllable. Also, aportion of the plurality of series stacked high frequency powerconverter cells may be arranged with parallel outputs. At least one ofthe plurality of series stacked high frequency power converter cells mayinclude one or more switched capacitors. Further, at least one of theplurality of series stacked high frequency power converter cells mayinclude at least one switched capacitor and a DC/DC regulatingconverter. The DC/DC regulating converter may be disposed in series withthe at least one switched capacitor.

The method may further include determining an amplitude of the varyinginput voltage signal. The method may also include controlling the seriesstacked high frequency power converter cells to produce the output basedon the amplitude of the varying input voltage signal. The controllingmay include soft switching of the plurality of series stacked highfrequency power converter cells. Further, the controlling may be basedon an instantaneous amplitude of the varying input voltage signal, alocal average of the varying input voltage signal, and the like.

In an embodiment, the controlling may include operating at least onehigh frequency power converter cell bypass function for the plurality ofseries stacked high frequency power converter cells. The controlling mayfurther include maintaining efficiency of the plurality of seriesstacked high frequency power converter cells above a minimum efficiencythreshold. In another embodiment, the minimum efficiency threshold maybe seventy percent, seventy-five percent, eighty percent, and the like.In addition, the controlling may include passive switched capacitorvoltage balancing. The method may further include an output stage thatmay facilitate configuring a parallel output combination of theplurality of series stacked high frequency power converter cells.

In yet another aspect, the present invention provides a method. Themethod may include receiving a varying input voltage signal to beapplied to a plurality of series stacked high frequency power convertercells. The plurality of series stacked high frequency power convertercells for producing an output from the varying input voltage signal. Inan embodiment, the varying input voltage signal may be an AC linesignal. Further, the output may be a DC voltage, a fixed current, andthe like. In an embodiment, individual cells of the plurality of seriesstacked high frequency power converter cells may be activated atdifferent determined amplitudes as the amplitude of the varying inputvoltage signal varies. The individual cells of the plurality of seriesstacked high frequency power converter cells may be deactivated atdifferent amplitudes as the determined amplitude of the varying inputvoltage signal decreases. Further, the individual cells of the pluralityof series stacked high frequency power converter cells may be bypassedat different determined amplitudes as the determined amplitude of thevarying input voltage signal decreases.

In another embodiment, each of the plurality of series stacked highfrequency power converter cells may be separately controllable. Also, aportion of the plurality of series stacked high frequency powerconverter cells may be arranged with parallel outputs. At least one ofthe plurality of series stacked high frequency power converter cells mayinclude one or more switched capacitors. Further, at least one of theplurality of series stacked high frequency power converter cells mayinclude at least one switched capacitor and a DC/DC regulatingconverter. The DC/DC regulating converter may be disposed in series withthe at least one switched capacitor.

The method may further include determining an amplitude of the varyinginput voltage signal. The method may also include controlling the seriesstacked high frequency power converter cells to produce the output basedon the amplitude of the varying input voltage signal. The controllingmay include soft switching of the plurality of series stacked highfrequency power converter cells. Further, the controlling may be basedon an instantaneous amplitude of the varying input voltage signal, alocal average of the varying input voltage signal, and the like.

In an embodiment, the controlling may include operating at least onehigh frequency power converter cell bypass function for the plurality ofseries stacked high frequency power converter cells. The controlling mayfurther include maintaining efficiency of the plurality of seriesstacked high frequency power converter cells above a minimum efficiencythreshold. In another embodiment, the minimum efficiency threshold maybe seventy percent, seventy-five percent, eighty percent, and the like.In addition, the controlling may include passive switched capacitorvoltage balancing. The method may further include an output stage thatmay facilitate configuring a parallel output combination of theplurality of series stacked high frequency power converter cells. In anembodiment, the requirement of the output may be a current requirement,a voltage requirement, a ripple requirement, a power requirement, anisolation requirement, and the like.

In still another aspect, the present invention provides a method. Themethod may include receiving a varying input voltage signal to beapplied to a plurality of series stacked high frequency power convertercells. The plurality of series stacked high frequency power convertercells for producing an output from the varying input voltage signal. Inan embodiment, the varying input voltage signal may be an AC linesignal. Further, the output may be a DC voltage, a fixed current, andthe like. In an embodiment, individual cells of the plurality of seriesstacked high frequency power converter cells may be activated atdifferent determined amplitudes as the amplitude of the varying inputvoltage signal varies. The individual cells of the plurality of seriesstacked high frequency power converter cells may be deactivated atdifferent amplitudes as the determined amplitude of the varying inputvoltage signal decreases. Further, the individual cells of the pluralityof series stacked high frequency power converter cells may be bypassedat different determined amplitudes as the determined amplitude of thevarying input voltage signal decreases.

In another embodiment, each of the plurality of series stacked highfrequency power converter cells may be separately controllable. Also, aportion of the plurality of series stacked high frequency powerconverter cells may be arranged with parallel outputs. At least one ofthe plurality of series stacked high frequency power converter cells mayinclude one or more switched capacitors. Further, at least one of theplurality of series stacked high frequency power converter cells mayinclude at least one switched capacitor and a DC/DC regulatingconverter. The DC/DC regulating converter may be disposed in series withthe at least one switched capacitor.

The method may further include determining an amplitude of the varyinginput voltage signal. The method may also include controlling the seriesstacked high frequency power converter cells to produce the output basedon the amplitude of the varying input voltage signal. The controllingmay include soft switching of the plurality of series stacked highfrequency power converter cells. Further, the controlling may be basedon an instantaneous amplitude of the varying input voltage signal, alocal average of the varying input voltage signal, and the like.

In an embodiment, the controlling may include operating at least onehigh frequency power converter cell bypass function for the plurality ofseries stacked high frequency power converter cells. The controlling mayfurther include maintaining efficiency of the plurality of seriesstacked high frequency power converter cells above a minimum efficiencythreshold. In another embodiment, the minimum efficiency threshold maybe seventy percent, seventy-five percent, eighty percent, and the like.In addition, the controlling may include passive switched capacitorvoltage balancing. The method may further include an output stage thatmay facilitate configuring a parallel output combination of theplurality of series stacked high frequency power converter cells.Further, the feedback may be a measure of output current.

In yet another aspect, the present invention provides a method. Themethod may include receiving a varying input voltage signal to beapplied to a plurality of series stacked high frequency power convertercells. The plurality of series stacked high frequency power convertercells for producing an output. The input voltage may be greater thanthat which may be sustainable by any one of the plurality of cells. Inan embodiment, the varying input voltage signal may be an AC linesignal. Further, the output may be a DC voltage, a fixed current, andthe like. In an embodiment, individual cells of the plurality of seriesstacked high frequency power converter cells may be activated atdifferent determined amplitudes as the amplitude of the varying inputvoltage signal varies. The individual cells of the plurality of seriesstacked high frequency power converter cells may be deactivated atdifferent amplitudes as the determined amplitude of the varying inputvoltage signal decreases. Further, the individual cells of the pluralityof series stacked high frequency power converter cells may be bypassedat different determined amplitudes as the determined amplitude of thevarying input voltage signal decreases.

In another embodiment, each of the plurality of series stacked highfrequency power converter cells may be separately controllable. Also, aportion of the plurality of series stacked high frequency powerconverter cells may be arranged with parallel outputs. At least one ofthe plurality of series stacked high frequency power converter cells mayinclude one or more switched capacitors. Further, at least one of theplurality of series stacked high frequency power converter cells mayinclude at least one switched capacitor and a DC/DC regulatingconverter. The DC/DC regulating converter may be disposed in series withthe at least one switched capacitor.

The method may also include controlling the series stacked highfrequency power converter cells distribute the input voltage among aportion of the plurality of power converter cells so that no cell mayreceive a portion of the input that exceeds that which may besustainable by the cell. The controlling may include soft switching ofthe plurality of series stacked high frequency power converter cells.Further, the controlling may be based on an instantaneous amplitude ofthe varying input voltage signal, a local average of the varying inputvoltage signal, and the like.

In an embodiment, the controlling may include operating at least onehigh frequency power converter cell bypass function for the plurality ofseries stacked high frequency power converter cells. The controlling mayfurther include maintaining efficiency of the plurality of seriesstacked high frequency power converter cells above a minimum efficiencythreshold. In another embodiment, the minimum efficiency threshold maybe seventy percent, seventy-five percent, eighty percent, and the like.In addition, the controlling may include passive switched capacitorvoltage balancing. The method may further include an output stage thatmay facilitate configuring a parallel output combination of theplurality of series stacked high frequency power converter cells.Further, each cell of the plurality of cells may be silicon-based.

In another aspect, the present invention provides a method. The methodmay include receiving a varying input voltage signal to be applied to aplurality of series stacked high frequency power converter cells. Theplurality of series stacked high frequency power converter cells forproducing an output from the varying input voltage signal. In anembodiment, the varying input voltage signal may be an AC line signal.Further, the output may be a DC voltage, a fixed current, and the like.In an embodiment, individual cells of the plurality of series stackedhigh frequency power converter cells may be activated at differentdetermined amplitudes as the amplitude of the varying input voltagesignal varies. The individual cells of the plurality of series stackedhigh frequency power converter cells may be deactivated at differentamplitudes as the determined amplitude of the varying input voltagesignal decreases. Further, the individual cells of the plurality ofseries stacked high frequency power converter cells may be bypassed atdifferent determined amplitudes as the determined amplitude of thevarying input voltage signal decreases.

In another embodiment, each of the plurality of series stacked highfrequency power converter cells may be separately controllable. Also, aportion of the plurality of series stacked high frequency powerconverter cells may be arranged with parallel outputs. At least one ofthe plurality of series stacked high frequency power converter cells mayinclude one or more switched capacitors. Further, at least one of theplurality of series stacked high frequency power converter cells mayinclude at least one switched capacitor and a DC/DC regulatingconverter. The DC/DC regulating converter may be disposed in series withthe at least one switched capacitor.

The method may further include determining an average of the outputvoltage. The method may also include synchronously controlling theseries stacked high frequency power converter cells to produce theoutput from the varying input voltage based on the determined average.The controlling may include soft switching of the plurality of seriesstacked high frequency power converter cells. Further, the controllingmay be based on an instantaneous amplitude of the varying input voltagesignal, a local average of the varying input voltage signal, and thelike.

In an embodiment, the controlling may include operating at least onehigh frequency power converter cell bypass function for the plurality ofseries stacked high frequency power converter cells. The controlling mayfurther include maintaining efficiency of the plurality of seriesstacked high frequency power converter cells above a minimum efficiencythreshold. In another embodiment, the minimum efficiency threshold maybe seventy percent, seventy-five percent, eighty percent, and the like.In addition, the controlling may include passive switched capacitorvoltage balancing. The method may further include an output stage thatmay facilitate configuring a parallel output combination of theplurality of series stacked high frequency power converter cells.

In another aspect, the present invention provides a method. The methodmay include receiving a single input voltage signal into a soft-switchedhigh frequency power converter. The soft-switched high frequency powerconverter may produce a plurality of output values. The plurality ofoutput values may be individually controllable. Further, the pluralityof output values may be individually selected from a current outputvalue and a voltage output value. In an embodiment, the single inputvoltage signal may be an AC input, a DC input, a fixed voltage, avarying voltage, and the like. The method may further includecontrolling the soft-switched high frequency power converter to producea first output during a first time interval for a first load and asecond output during a second time interval for a second load. Themethod may also include providing at least one load isolation controlsignal to facilitate bypassing the second load during the first timeinterval and bypassing the first load during the second time interval.

In an embodiment, the first output may be one of a current and avoltage. Further, the first output may be regulated during the firsttime interval. In another embodiment, the second output may be one of acurrent and a voltage. Further, the second output may be regulatedduring the second time interval. In embodiments, the voltage outputduring at least one of the first and second time intervals may be asubstantially fixed voltage. Further, each portion of the load mayreceive a different output voltage, a substantially fixed current, adifferent current, and the like. Power from the single input voltagesignal may be time-division-multiplexed among the outputs. In addition,at least one of the first load and the second load may be a portion of astring of LEDs. Also, the output provided during each time interval maydrive separate LEDs to facilitate achieving a substantially constantcolor temperature light output.

In yet another aspect, the present invention provides a method. Themethod may include receiving a single input voltage signal into asoft-switched high frequency power converter including a plurality ofseries stacked high frequency power converter cells. The soft-switchedhigh frequency power converter may produce a plurality of output values.Each of the plurality of series stacked high frequency power convertercells may be separately controllable. Further, a portion of theplurality of series stacked high frequency power converter cells may bearranged with parallel outputs. In an embodiment, at least one of theplurality of series stacked high frequency power converter cells mayinclude one or more switched capacitors. In another embodiment, the atleast one of the plurality of series stacked high frequency powerconverter cells may include at least one switched capacitor and a DC/DCregulating converter. The DC/DC regulating converter may be disposed inseries with the at least one switched capacitor.

The method may further include controlling the soft-switched highfrequency power converter cells to produce a first output during a firsttime interval for a first load and a second output during a second timeinterval for a second load. The method may also include providing atleast one load isolation control signal to facilitate bypassing thesecond load during the first time interval and bypassing the first loadduring the second time interval. The controlling may include softswitching of the plurality of series stacked high frequency powerconverter cells. The controlling may also include operating at least onehigh frequency power converter cell bypass function for the plurality ofseries stacked high frequency power converter cells.

Further, the controlling may include maintaining efficiency of theplurality of series stacked high frequency power converter cells above aminimum efficiency threshold. In an embodiment, the minimum efficiencythreshold may be seventy percent, seventy-five percent, eighty percent,and the like. The controlling may further include passive switchedcapacitor voltage balancing. In an embodiment, the method may include anoutput stage that may facilitate configuring a parallel outputcombination of the plurality of series stacked high frequency powerconverter cells.

In an embodiment, the first output may be one of a current and avoltage. The first output may be regulated during the first timeinterval. In another embodiment, the second output may be one of acurrent and a voltage. The second output may be regulated during thesecond time interval. Further, the plurality of output values may beindividually controllable. The plurality of output values may beindividually selected from a current output value and a voltage outputvalue. In an embodiment, the single input voltage signal may be an ACinput, a DC input, a fixed voltage, a varying voltage, and the like.

In another embodiment, the voltage output during at least one of thefirst and second time intervals may be a substantially fixed voltage.Further, each portion of the loads may receive a different outputvoltage, a substantially fixed current, a different current, and thelike. At least one of the first load and the second load may be aportion of a string of LEDs. The output provided during each timeinterval may drive separate LEDs to facilitate achieving a substantiallyconstant color temperature light output.

In still another aspect, the present invention provides a method. Themethod may include receiving a single input voltage signal into asoft-switched high frequency power converter for producing a pluralityof output values on an output port. The method may further includecontrolling the soft-switched high frequency power converter to producea first output during a first time interval and a second output during asecond time interval. The controlling may include maintaining efficiencyof the soft-switched high frequency power converter above a minimumefficiency threshold. In an embodiment, the minimum efficiency thresholdmay be seventy percent, seventy-five percent, eighty percent, and thelike. The controlling may further include passive switched capacitorvoltage balancing. In an embodiment, the first output may be one of acurrent and a voltage. The first output may be regulated during thefirst time interval. In another embodiment, the second output may be oneof a current and a voltage. The second output may be regulated duringthe second time interval.

Further, the plurality of output values may be individuallycontrollable. The plurality of output values may be individuallyselected from a current output value and a voltage output value. Thesingle input voltage signal may be an AC input, a DC input, a fixedvoltage, a varying voltage, and the like. The voltage output during atleast one of the first and second time intervals may be a substantiallyfixed voltage. The method may also include connecting a string of LEDssubstantially in parallel to the output port. The string of LEDs may beconfigured so that a first portion of the LEDs may be controllable toform a circuit with the soft-switched high frequency power converterduring the first time interval and a second portion of the LEDs may becontrollable to form a circuit with the soft-switched high frequencypower converter during the second time interval to facilitate achievingsubstantially constant color temperature light.

Further, each LED in the string of LEDs may receive a different outputvoltage, a substantially fixed current, a different current, and thelike. In addition, power from the single input voltage signal may betime-division-multiplexed among the outputs. The soft-switched highfrequency power converter may employ time-division-multiplexing of theoutput port.

In another aspect, the present invention provides a method. The methodmay include receiving a single input voltage signal into a soft-switchedhigh frequency power converter for producing a plurality of outputvalues on an output port. The method may further include controlling thesoft-switched high frequency power converter to output a first outputduring a first time interval for a first motherboard circuit load and asecond output during a second time interval for a second motherboardcircuit load. The controlling may include maintaining efficiency of theplurality of soft-switched high frequency power converter above aminimum efficiency threshold. In an embodiment, the minimum efficiencythreshold may be seventy percent, seventy-five percent, eighty percent,and the like.

The controlling may further include passive switched capacitor voltagebalancing. In an embodiment, the first output may be one of a currentand a voltage. The first output may be regulated during the first timeinterval. In another embodiment, the second output may be one of acurrent and a voltage. The second output may be regulated during thesecond time interval. Further, the plurality of output values may beindividually controllable. The plurality of output values may beindividually selected from a current output value and a voltage outputvalue. In an embodiment, the single input voltage signal may be an ACinput, a DC input, a fixed voltage, a varying voltage, and the like.

Further, the voltage output during at least one of the first and secondtime intervals may be a substantially fixed voltage. The method may alsoinclude providing at least one output to facilitate disconnecting thesecond motherboard circuit load from the converter during the first timeinterval and disconnecting the first motherboard circuit load from thesoft-switched high frequency power converter during the second timeinterval. In an embodiment, the first motherboard circuit load and thesecond motherboard circuit load may receive a different output voltage,a substantially fixed current, a different current, and the like. Inaddition, power from the single input voltage signal may betime-division-multiplexed among the outputs.

In yet another aspect, the present invention provides a method. Themethod may include receiving a single input voltage signal into asoft-switched high frequency power converter for producing a pluralityof voltages on an output. The method may further include connecting atleast one color changing LED to the output. The method may also includecontrolling the soft-switched high frequency power converter to producea first color out of the at least one color changing LED during a firsttime interval and a second color during a second time interval. Further,the controlling may include maintaining efficiency of the soft-switchedhigh frequency power converter above a minimum efficiency threshold. Inan embodiment, the minimum efficiency threshold may be seventy percent,seventy-five percent, eighty percent, and the like. The controlling mayfurther include passive switched capacitor voltage balancing.

In an embodiment, the first color may be regulated during the first timeinterval. In another embodiment, the second color may be regulatedduring the second time interval. The plurality of voltages may beindividually controllable. The plurality of voltages may be individuallyselected from a current output value and a voltage output value. In anembodiment, the single input voltage signal may be an AC input, a DCinput, a fixed voltage, a varying voltage, and the like. Further, thevoltage output during at least one of the first and second timeintervals may be a substantially fixed voltage.

In embodiments, each LED in the at least one color changing LED mayreceive a different output voltage, a substantially fixed current, adifferent current, and the like. In addition, power from the singleinput voltage signal may be time-division-multiplexed among the outputs.Further, the soft-switched high frequency power converter may employtime-division-multiplexing of the output port.

In another aspect, the present invention provides a system. The systemmay include a VHF power converter adapted for driving an LED-basedlight. The VHF power converter may include at least one soft-switchedpower converter cell and at least one inductor. Each inductor mayinclude an inductance value no greater than one micro henry. In anembodiment, the at least one inductor may be a PCB etch-based inductor.Further, the at least one soft-switched power converter cell may besilicon-based. The at least one soft-switched power converter cell mayswitch at greater than 5 MHz.

In yet another aspect, the present invention provides a system. Thesystem may include a VHF power converter adapted for driving anLED-based light. The power converter may include at least onesoft-switched power converter cell and at least one inductor. Eachinductor may include an inductance value no greater than five microhenries. In an embodiment, the at least one inductor may be a PCBetch-based inductor. Further, the at least one soft-switched powerconverter cell may be silicon-based. The at least one soft-switchedpower converter cell may switch at greater than 5 MHz.

In still another aspect, the present invention provides a system. Thesystem may include a high efficiency VHF power converter adapted fordriving an LED-based light. The power converter may include at least onesoft-switched power converter cell and a plurality of electroniccomponents. Further, none of the plurality of electronic components mayhave an inductance value greater than one micro henry. In an embodiment,the at least one inductor may be a PCB etch-based inductor. Further, theat least one soft-switched power converter cell may be silicon-based.The at least one soft-switched power converter cell may switch atgreater than 5 MHz.

In another aspect, the present invention provides a system. The systemmay include a stacked-cell, high efficiency, soft-switched AC to DCpower converter. The power converter may include at least onesoft-switched power converter cell and a plurality of electroniccomponents. Further, none of the plurality of electronic components mayhave an inductance value greater than one micro henry. Further, the atleast one soft-switched power converter cell may be silicon-based. Theat least one soft-switched power converter cell may switch at greaterthan 5 MHz.

In another aspect, the present invention provides a system. The systemmay include a high efficiency, soft-switched power converter forconverting line AC to DC. The power converter may include a plurality ofelectronic components. Further, none of the plurality of electroniccomponents may have an inductance value greater than five micro henries.Further, the at least one soft-switched power converter cell may besilicon-based. The at least one soft-switched power converter cell mayswitch at greater than 5 MHz.

In yet another aspect, the present invention provides a stacked cellswitching power converter. The stacked cell switching power convertermay include a plurality of stacked power cells flexibly connected toreceive an AC input signal in series and provide a DC output. Thestacked cell switching power converter may further include a controllerfor configuring the plurality of stacked power cells and the flexibleconnection to receive the DC input signal and for facilitating fullyresonant switching. The stacked cell switching power converter may alsoinclude one or more output synchronous rectifiers for receiving anoutput from each of a portion of the plurality of stacked power cells inparallel and for delivering a combined DC output to a load. Further,each of the plurality of stacked power cells may be separatelycontrollable. In an embodiment, a portion of the plurality of stackedpower cells may be arranged with parallel outputs.

The stacked cell switching power converter may further include an outputstage that may facilitate configuring a parallel output combination ofthe plurality of stacked power cells. Further, at least one of theplurality of stacked power cells may include one or more switchedcapacitors. At least one of the plurality of stacked power cells mayinclude at least one switched capacitor and a DC/DC regulatingconverter. The DC/DC regulating converter may be disposed in series withthe at least one switched capacitor.

In an embodiment, the controlling may include soft switching of theplurality of stacked power cells. The controlling may further includeoperating at least one power cell bypass function for the plurality ofstacked power cells. The controlling may also include maintainingconverter efficiency above a minimum efficiency threshold. In anotherembodiment, the minimum efficiency threshold may be seventy percent,seventy-five percent, eighty percent, and the like. Further, thecontrolling may include passive switched capacitor voltage balancing.

In still another aspect, the present invention provides a method ofconverting AC to DC. The method may include disposing a plurality offully resonant switching VHF power converter cells into a series stackto receive an AC input signal and output a DC signal therefrom. Each ofthe plurality of fully resonant switching VHF power converter cells maybe separately controllable. Further, a portion of the plurality of fullyresonant switching VHF power converter cells may be arranged withparallel outputs. The output may facilitate powering an LED-based lightwith substantially no visible light flicker. In an embodiment, theoutput may include substantially no ripple voltage. Further,substantially no AC frequency harmonics may be propagated to the output.

The method may further include connecting the DC signal output from atleast a portion of the plurality of fully resonant switching VHF powerconverter cells in parallel to form a combined output. The method mayalso include synchronously rectifying the combined output. In addition,the method may include controlling the plurality of fully resonantswitching VHF power converter cells for facilitating fully resonantswitching and controlling the output rectifier for synchronousrectification. In an embodiment, the method may further include anoutput stage that may facilitate configuring a parallel outputcombination of the plurality of fully resonant switching VHF powerconverter cells. Further, at least one of the plurality of fullyresonant switching VHF power converter cells may include one or moreswitched capacitors.

In another embodiment, at least one of the plurality of fully resonantswitching VHF power converter cells may include at least one switchedcapacitor and a DC/DC regulating converter. The DC/DC regulatingconverter may be disposed in series with the at least one switchedcapacitor. The controlling may include soft switching of the pluralityof fully resonant switching VHF power converter cells. Further, thecontrolling may include operating at least one power cell bypassfunction for the plurality of fully resonant switching VHF powerconverter cells. The controlling may also include maintaining converterefficiency above a minimum efficiency threshold.

In an embodiment, the minimum efficiency threshold may be seventypercent, seventy-five percent, eighty percent, and the like. Thecontrolling may also include passive switched capacitor voltagebalancing. The output may facilitate powering an LED-based light withsubstantially no visible light flicker. The output may includesubstantially no ripple voltage. Further, substantially no AC frequencyharmonics may be propagated to the output.

In another aspect, the present invention provides a method of convertingDC to DC. The method may include disposing a plurality of fully resonantswitching VHF power converter cells into a series stack to receive a DCinput signal and output a DC signal therefrom. Each of the plurality offully resonant switching VHF power converter cells may be separatelycontrollable. Further, a portion of the plurality of fully resonantswitching VHF power converter cells may be arranged with paralleloutputs. The method may further include connecting the DC signal outputfrom at least a portion of the plurality of fully resonant switching VHFpower converter cells in parallel to form a combined output. The methodmay also include synchronously rectifying the combined output. Inaddition, the method may include controlling the plurality of fullyresonant switching VHF power converter cells for facilitating resonantswitching. The method may further include controlling the outputrectifier for synchronous rectification.

In an embodiment, the method may include an output stage that mayfacilitate configuring a parallel output combination of the plurality offully resonant switching VHF power converter cells. Further, at leastone of the plurality of fully resonant switching VHF power convertercells may include one or more switched capacitors. At least one of theplurality of fully resonant switching VHF power converter cells mayinclude at least one switched capacitor and a DC/DC regulatingconverter. The DC/DC regulating converter may be disposed in series withthe at least one switched capacitor.

Further, controlling the plurality of fully resonant switching VHF powerconverter cells may include soft switching of the plurality of fullyresonant switching VHF power converter cells. The controlling theplurality of fully resonant switching VHF power converter cells mayinclude operating at least one power cell bypass function for theplurality of fully resonant switching VHF power converter cells.Furthermore, controlling the plurality of fully resonant switching VHFpower converter cells may include maintaining converter efficiency abovea minimum efficiency threshold. In an embodiment, the minimum efficiencythreshold may be seventy percent, seventy-five percent, eighty percent,and the like. The controlling the plurality of fully resonant switchingVHF power converter cells may also include passive switched capacitorvoltage balancing.

In yet another aspect, the present invention provides a method ofconverting DC to DC. The method may include disposing a plurality offully resonant switching VHF power converter cells into a serial stackto receive a DC input signal and output a DC signal therefrom. Themethod may further include connecting the DC signal output from at leasta portion of the plurality of converter cells in parallel to form acombined output. The method may also include synchronously rectifyingthe combined output. Further, the method may include controlling thepower converter cells for facilitating resonant switching. In addition,the method may include controlling the power converter cells forfacilitating resonant switching. Each of the plurality of fully resonantswitching VHF power converter cells may be separately controllable.Further, a portion of the plurality of fully resonant switching VHFpower converter cells may be arranged with parallel outputs.

In an embodiment, the method may further include an output stage thatmay facilitate configuring a parallel output combination of theplurality of fully resonant switching VHF power converter cells. Atleast one of the plurality of fully resonant switching VHF powerconverter cells may include one or more switched capacitors. Further, atleast one of the plurality of fully resonant switching VHF powerconverter cells may include at least one switched capacitor and a DC/DCregulating converter. The DC/DC regulating converter may be disposed inseries with the at least one switched capacitor.

In another embodiment, controlling the plurality of fully resonantswitching VHF power converter cells may include soft switching of theplurality of fully resonant switching VHF power converter cells. Thecontrolling the plurality of fully resonant switching VHF powerconverter cells may include operating at least one power cell bypassfunction for the plurality of fully resonant switching VHF powerconverter cells. Further, the controlling the plurality of fullyresonant switching VHF power converter cells may include maintainingconverter efficiency above a minimum efficiency threshold. In anembodiment, the minimum efficiency threshold may be seventy percent,seventy-five percent, eighty percent, and the like. The controlling theplurality of fully resonant switching VHF power converter cells may alsoinclude passive switched capacitor voltage balancing. In addition, theoutput may facilitate powering an LED-based light with substantially novisible light flicker. The output may include substantially no ripplevoltage.

In another aspect of the present invention, a method of multi-path powerfactor correction is provided. The method may include providing aplurality of energy transfer paths from an voltage-varying input to anoutput. The method may also include delivering a first fraction ofavailable input energy to one or more energy storage networks at theinput of at least one of the plurality of energy transfer paths.Further, the method may include delivering a second fraction ofavailable input energy to the output. In addition, the method mayinclude adjusting the first fraction and second fraction forfacilitating outputting a substantially constant output and forcontrolling the energy drawn from the input.

In an embodiment, the controlling may include controlling a VHF powerconverter comprising the plurality of energy paths. Further, a portionof the plurality of energy paths may include a plurality ofsoft-switched power converter cells. The power factor correcting mayinclude switching at least one of the interleaved power converter cells.The switching may produce unity power factor. Further, a portion of theplurality of energy paths may include a plurality of soft-switchedstacked-cell power converters. A portion of the stacked-cell powerconverters may be connected to a common node. In an embodiment, thepower converter may operate above 5 MHz.

In yet another aspect of the present invention, a VHF switching powerconverter is provided. The VHF switching power converter may include atleast one power cell configured to receive an AC line input signal toprovide an output suitable for powering an LED. Each of the at least onepower cell may be separately controllable. Further, a portion of the atleast one power cell may be arranged with parallel outputs. The VHFswitching power converter may also include a controller for configuringthe at least one power cell to receive the input signal and forfacilitating switching the power converter at a frequency in excess of 5MHz. In addition, the VHF switching power converter may include anoutput stage for receiving an output from the at least one power celland for delivering a combined output to an LED.

In an embodiment, the VHF switching power converter may further includean output stage that may facilitate configuring a parallel outputcombination of the at least one power cell. The at least one power cellmay include one or more switched capacitors. Further, the at least onepower cell may include at least one switched capacitor and a DC/DCregulating converter. The DC/DC regulating converter may be disposed inseries with the at least one switched capacitor. The controller softswitching of the at least one power cell. In an embodiment, the minimumefficiency threshold may be seventy percent, seventy-five percent,eighty percent, and the like. Further, the controlling the at least onepower cell may include passive switched capacitor voltage balancing. TheVHF switching power converter may operate above 5 MHz. In addition,powering the LED-based light may not require use of electrolyticcapacitors.

In another aspect of the present invention, a method of powering an LEDis provided. The method may include receiving an AC line input signalwith at least one VHF switching power cell. The method may furtherinclude operating the power cell at a frequency in excess of 5 MHz forproviding a DC output suitable for powering an LED. The method may alsoinclude receiving an output from the at least one VHF switching powercell to provide a combined output. In addition, the method may includedelivering the combined output to an LED. Each of the at least one powercell may be separately controllable. A portion of the at least one VHFswitching power cell may be arranged with parallel outputs.

In an embodiment, the method may further include an output stage thatmay facilitate configuring a parallel output combination of the at leastone VHF switching power cell. The at least one VHF switching power cellmay include one or more switched capacitors. The at least one VHFswitching power cell may include at least one switched capacitor and aDC/DC regulating converter. The DC/DC regulating converter may bedisposed in series the at least one switched capacitor.

In yet another aspect of the present invention, a stacked cellsoft-switchable power converter is provided. The stacked cellsoft-switchable power converter may include a plurality of stacked powercells flexibly connected to receive an AC input signal and provide anoutput suitable for powering an LED. The stacked cell soft-switchablepower converter may also include a controller for configuring the powercells and the flexible connection to receive the input sign. Further,the stacked cell soft-switchable power converter may include an outputstage for receiving an output from each of a portion of the plurality ofstacked power cells and for delivering a combined DC output to an LED.

In an embodiment, each of the plurality of stacked power cells may beseparately controllable. Further, a portion of the plurality of stackedpower cells may be arranged with parallel outputs. The stacked cellsoft-switchable power converter may further include an output stage thatmay facilitate configuring a parallel output combination of theplurality of stacked power cells. The plurality of stacked power cellsmay include one or more switched capacitors. Further, the plurality ofstacked power cells may include at least one switched capacitor and aDC/DC regulating converter. The DC/DC regulating converter may bedisposed in series the at least one switched capacitor.

In another embodiment, the controller operating at least one power cellmay bypass function for at least one power cell. Further, the controllermay maintain converter efficiency above a minimum efficiency threshold.The minimum efficiency threshold may be seventy percent, seventy-fivepercent, eighty percent, and the like. The controller may be configuredfor passive switched capacitor voltage balancing. Further, powering theLED-based light may include controlling the operation of at least onecell in the stacked power cell. The powering may includepulse-width-modulating at least one cell in the stacked power cell.Further, the powering may include power factor correcting.

In an aspect, the present invention provides a method. The method mayinclude receiving an input voltage signal to be applied to a pluralityof series stacked very high frequency power converter cells. Theplurality of series stacked very high frequency power converter cellsfor producing an output voltage or current. The method may also includedetermining an output current. The method may further includecontrolling a portion of the plurality of series stacked high frequencypower converter cells through pulse-width modulation to control theoutput current. Each of the plurality of series stacked very highfrequency power converter cells may be separately controllable. Aportion of the plurality of series stacked very high frequency powerconverter cells may be arranged with parallel outputs.

In an embodiment, the method may include an output stage that mayfacilitate configuring a parallel output combination of the plurality ofseries stacked very high frequency power converter cells. Further, atleast one of the plurality of series stacked very high frequency powerconverter cells may include one or more switched capacitors. At leastone of the plurality of series stacked very high frequency powerconverter cells may include at least one switched capacitor and a DC/DCregulating converter. The DC/DC regulating converter may be disposed inseries the at least one switched capacitor. The controlling theplurality of series stacked very high frequency power converter cellsmay include soft switching of the plurality of series stacked very highfrequency power converter cells.

Further, the controlling the plurality of series stacked very highfrequency power converter cells may include operating at least one powercell bypass function for the plurality of series stacked very highfrequency power converter cells. The controlling the plurality of seriesstacked very high frequency power converter cells may includemaintaining converter efficiency above a minimum efficiency threshold.The minimum efficiency threshold may be seventy percent, seventy-fivepercent, eighty percent, and the like. Further, the controlling theplurality of series stacked very high frequency power converter cellsmay include passive switched capacitor voltage balancing.

In another aspect of the present invention, a system for providing highisolation AC to DC power conversion within a bounding box no larger thanfive US quarter dollar coins is provided. The system may include a powercell disposed to receive an AC input signal and provide a DC output. Thesystem may also include a controller for configuring the power cell toreceive the input signal. Further, the system may include an outputstage for receiving an output from the power cell and for delivering anisolated output to a load. In an embodiment, the controller may softswitch the power cell. Further, the controller may operate the powercell bypass function for the power cell. The controller may maintainconverter efficiency above a minimum efficiency threshold. The minimumefficiency threshold may be seventy percent, seventy-five percent,eighty percent, and the like. In an embodiment, the controller may beconfigured for passive switched capacitor voltage balancing. Thebounding box no larger than five US quarter dollar coins may include acubic volume of less than 4050 cubic millimeters.

In yet another aspect, the present invention may include a system forproviding high isolation AC to DC power conversion within a bounding boxno larger than five US quarter dollar coins. The system may include asoft-switchable power cell disposed to receive an AC input signal andprovide a DC output. The system may further include a VHF speedcontroller for configuring the soft-switchable power cell to receive theinput signal. Also, the system may include a transformer stage forreceiving an output from the soft-switchable power cell and fordelivering an isolated output to a load. The VHF speed controller maysoft switch the soft-switchable power cell. Further, the VHF speedcontroller may operate the soft-switchable power cell bypass functionfor the power cell. The VHF speed controller may maintain converterefficiency above a minimum efficiency threshold. In an embodiment, theminimum efficiency threshold may be seventy percent, seventy-fivepercent, eighty percent, and the like. In addition, the VHF speedcontroller may be configured for passive switched capacitor voltagebalancing.

In still another aspect, the present invention provides a system forproviding high isolation AC to DC power conversion within a bounding boxno larger than five US quarter dollar coins. The system may include aplurality of soft-switchable power cells flexibly connected to receivean input signal in series and provide an output. The system may alsoinclude a controller for configuring the plurality of soft-switchablepower cells and the flexible connection to receive the input signal.Further, the system may include a transformer stage for receivingoutputs from a portion of the plurality of soft-switchable power cellsand for delivering a combined isolated output to a load. Each of theplurality of soft-switchable power cells may be separately controllable.Further, a portion of the plurality of soft-switchable power cells maybe arranged with parallel outputs.

In an embodiment, the system may further include an output stage thatmay facilitate configuring a parallel output combination of theplurality of soft-switchable power cells. The plurality ofsoft-switchable power cells may include one or more switched capacitors.The plurality of soft-switchable power cells may include at least oneswitched capacitor and a DC/DC regulating converter. The DC/DCregulating converter may be disposed in series the at least one switchedcapacitor. Further, the controller may soft switch the soft-switchablepower cell. The controller may operate the soft-switchable power cellbypass function for the power cell. The controller may also maintainconverter efficiency above a minimum efficiency threshold. In anembodiment, the minimum efficiency threshold may be seventy percent,seventy-five percent, eighty percent, and the like. The controller maybe configured for passive switched capacitor voltage balancing. Further,a bounding box no larger than five US quarter dollar coins may include acubic volume of less than 4050 cubic millimeters.

In another aspect, the present invention provides a power converter forproviding a DC output comprising arbitrarily small ripple from an ACsource within a bounding box no larger than five US quarter dollarcoins. The power converter may include a power cell disposed to receivean input signal and provide an output. The power converter may alsoinclude a controller for controlling the power cell to convert the inputsignal to an output comprising arbitrarily small ripple. Further, thepower converter may include a feedback path for providing arepresentation of the output to the controller to facilitate providingthe arbitrarily small ripple. The controller may soft switch the powercell. The controller may operate the power cell bypass function for thepower cell. The controller may maintain converter efficiency above aminimum efficiency threshold.

In an embodiment, the minimum efficiency threshold may be seventypercent, seventy-five percent, eighty percent, and the like. Thecontroller may also be configured for passive switched capacitor voltagebalancing. Further, a bounding box no larger than five US quarter dollarcoins may include a cubic volume of less than 4050 cubic millimeters.

The present invention further provides a VHF power converter forproviding a DC output comprising arbitrarily small ripple from an ACsource within a bounding box no larger than five US quarter dollarcoins. The VHF power converter may include a soft-switchable power celldisposed to receive an input signal and provide an output. The VHF powerconverter may further include a VHF frequency controller for controllingthe power cell to convert the input signal to an output comprisingarbitrarily small ripple. In addition, the VHF power converter mayinclude a feedback path for providing a representation of the output tothe controller to facilitate providing the arbitrarily small ripple. Thecontroller may soft switch the power cell. The controller may operatethe power cell bypass function for the power cell.

In an embodiment, the controller may maintain converter efficiency abovea minimum efficiency threshold. The minimum efficiency threshold may beseventy percent, seventy-five percent, eighty percent, and the like.Further, the controller may be configured for passive switched capacitorvoltage balancing. In another embodiment, the bounding box no largerthan five US quarter dollar coins may include a cubic volume of lessthan 4050 cubic millimeters.

In still another aspect of the present invention, a high efficiency VHFpower converter for providing at least two watts of DC output power froman AC source within a bounding box no larger than five US quarter dollarcoins is provided. The high efficiency VHF power converter may include asoft-switchable power cell disposed in the converter to receive an inputsignal and provide an output. The high efficiency VHF power convertermay further include a VHF frequency controller for controlling the powercell to produce at least two watts of power from the input signal withat least seventy percent conversion efficiency. The controller may softswitch the power cell. In addition, the controller may operate the powercell bypass function for the power cell.

In an embodiment, the controller may maintain converter efficiency abovea minimum efficiency threshold. The minimum efficiency threshold may beseventy percent, seventy-five percent, eighty percent, and the like. Thecontroller may be configured for passive switched capacitor voltagebalancing. In an embodiment, a bounding box no larger than five USquarter dollar coins may include a cubic volume of less than 4050 cubicmillimeters.

In another aspect, the present invention provides a high efficiency VHFpower converter for providing at least two watts of DC output power froman AC source within a bounding box no larger than five US quarter dollarcoin. The high efficiency VHF power converter may include asoft-switchable power cell disposed in the converter to receive an inputsignal and provide an output. Further, the high efficiency VHF powerconverter may include a VHF frequency controller for controlling thepower cell to produce at least two watts of power from the input signalwith at least seventy-five percent conversion efficiency. The controllermay soft switch the power cell.

In an embodiment, the controller may operate the power cell bypassfunction for the power cell. The controller may maintain converterefficiency above a minimum efficiency threshold. The minimum efficiencythreshold may be seventy percent, seventy-five percent, eighty percent,and the like. The controller may be configured for passive switchedcapacitor voltage balancing. In an embodiment, a bounding box no largerthan five US quarter dollar coins may include a cubic volume of lessthan 4050 cubic millimeters.

In still another aspect of the present invention, a high efficiency VHFpower converter for providing at least fifty watts of DC output powerwithin a bounding box no larger than three US quarter dollar coins isprovided. The high efficiency VHF power converter may include aplurality of series-stacked soft-switchable power cells disposed in theconverter to receive an input signal and provide at least fifty watts ofpower to an output. The high efficiency VHF power converter may alsoinclude a VHF frequency controller for controlling the plurality ofpower cells to produce the at least fifty watts of power from the inputsignal. In an embodiment, the bounding box no larger than three USquarter dollar coins may include a cubic volume of less than 2430 cubicmillimeters.

In yet another aspect of the present invention, a high efficiency VHFpower converter for providing at least fifteen watts of output powerwithin a bounding box no larger than one US quarter dollar coin isprovided. The high efficiency VHF power converter may include aplurality of series-stacked soft-switchable power cells disposed in theconverter to receive an input signal and provide at least fifteen wattsof power to an output. Further, the high efficiency VHF power convertermay include a VHF frequency controller for controlling the plurality ofpower cells to produce the at least fifteen watts of power from theinput signal. In an embodiment, the bounding box no larger than one USquarter dollar coin may include a cubic volume of less than 810 cubicmillimeters.

In an aspect of the methods and systems described herein, a method ofcontrol may include receiving a varying input voltage signal to beapplied to a plurality of series stacked high frequency power convertercells, the power converter cells for producing an output from thevarying input; determining an average of the input voltage; andsynchronously controlling the series stacked high frequency powerconverter cells to produce the output from the varying input voltagebased on the determined average.

In an aspect of the methods and systems described herein, a method ofcontrol may include receiving a varying input voltage signal to beapplied to a plurality of series stacked high frequency power convertercells, the power converter cells for producing an output from thevarying input; determining an average of the input current; andsynchronously controlling the series stacked high frequency powerconverter cells to produce the output from the varying input voltagebased on the determined average.

In an aspect of the methods and systems described herein, a method ofcontrol may include receiving a varying input voltage signal to beapplied to a plurality of series stacked high frequency power convertercells, the power converter cells for producing an output from thevarying input; determining an average of the output current; andsynchronously controlling the series stacked high frequency powerconverter cells to produce the output from the varying input voltagebased on the determined average.

In an aspect of the methods and systems described herein, a method ofcontrolling a stacked-cell VHF power converter may include sensing avoltage input to the converter; adjusting a by-pass function for atleast one stacked-cell based on the sensed input voltage; sensing theinput current; sensing the output current; and adjusting operation of atleast one stacked-cell to control the input current and the outputcurrent based at least in part on one of the sensed input current andthe sensed output current.

In an aspect of the methods and systems described herein, a method ofcontrolling a stacked-cell VHF power converter may include sensing avoltage input to the converter; adjusting a by-pass function for atleast one stacked-cell based on the sensed input voltage; sensing theinput current; sensing at least one of the output voltage and the outputcurrent; and adjusting operation of at least one stacked-cell to controlthe input voltage to at least one other stacked-cell based at least inpart on one of the sensed input voltage, the sensed input current, theoutput voltage, and the sensed output current.

These and other systems, methods, objects, features, and advantages ofthe present invention will be apparent to those skilled in the art fromthe following detailed description of the preferred embodiment and thedrawings. All documents mentioned herein are hereby incorporated intheir entirety by reference.

BRIEF DESCRIPTION OF THE FIGURES

The invention and the following detailed description of certainembodiments thereof may be understood by reference to the followingfigures:

FIG. 1 depicts a basic structure of a switching DC/DC converter;

FIG. 2 depicts a Class-E inverter joined with a series loaded resonantrectifier;

FIG. 3 depicts current and voltage waveforms of an AC/DC converter;

FIG. 4 depicts waveforms representing loss of ZVS as load is decreased;

FIG. 5 depicts resistance compression networks;

FIG. 6 depicts topology of a Φ₂ inverter;

FIG. 7 depicts a voltage waveform across a switch of the circuit of FIG.6;

FIG. 8 depicts a on-off modulation converter schematic;

FIG. 9 shows inverter and rectifier voltages for a plurality of inputvoltages;

FIG. 10 depicts a Class-E inverter connected to a rectifier dualcircuit;

FIG. 11 depicts a Φ₂ inverter connected to a rectifier dual circuit;

FIG. 12 depicts various configurations of series stacked cellembodiments;

FIG. 13 depicts two embodiments of a VHF converter system;

FIG. 14 depicts a switched cell based on a switched capacitor stagefollowed by a VHF stage;

FIG. 15 depicts a serial stacked cell VHF converter;

FIG. 16 depicts a timeline view of one rectified cycle of an 137.5 VACinput;

FIG. 17 depicts an input current control loop and an output currentcontrol loop;

FIG. 18 depicts an exemplary VHF converter architecture block diagram;

FIG. 19 depicts an embodiment of a VHF converter that maybe suitable foruse with MR16 lighting applications;

FIG. 20 depicts a bi-phase auxiliary power circuit;

FIG. 21 depicts a waveform of a rectified AC voltage with a currentwaveform that achieves unity power-factor;

FIG. 22 depicts a block diagram that illustrates one implementation ofpower factor correction;

FIG. 23 depicts simulated waveforms over a single AC line cycle for thepower factor correction embodiment of FIG. 22;

FIG. 24 depicts a switch network embodiment of a power factor correctioncircuit;

FIG. 25 depicts sample waveforms over a complete AC cycle for theembodiment of FIG. 24;

FIG. 26 depicts an example current waveform is presented that containsodd harmonics in addition to the fundamental;

FIG. 27 depicts a multi-channel embodiment of a VHF converter; and

FIG. 28 depicts an application of a VHF converter for replacing anincandescent bulb with a multiple LED light.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT(S)

Increasing the switching frequency of a switched-mode power supply(SMPS) is a goal that is widely sought after as a means to increasepower density and improve transient performance. However, increasingswitching frequency using conventional power converter topologies(boost, buck, flyback, etc.) results with significantly degradedefficiency. Additionally, as switching frequency is increased, powerdensity only increases until an optimal switching frequency is reached,at which point power density begins to decrease again. A new powerconverter architecture is described herein that breaks the bounds ofconventional techniques, enabling efficient high frequency operationwhile delivering increased power per converter volume.

Soft-switched resonant inverters have been developed for high efficiencyradio-frequency (RF) transmitter applications. These techniques havebeen adapted to form efficient DC/DC converters at switching frequenciesgreater than 100 MHz. The basic structure of this type of converter isshown in FIG. 1. The inverter stage takes DC power from the input anddelivers RF AC power to the transformation network. The transformationnetwork scales the AC signal to the appropriate level using eitherpassive components and/or a transformer. The rectifier takes AC powerfrom the transformation network and converters it back to DC.

Inverters that are suitable for efficient operation at VHF use resonanceand characteristics of the load to achieve zero-voltage switching.Resonant rectifier topologies are often used and can be modeled as animpedance in a describing function sense. The transformation stageserves to form an impedance match between the inverter and the rectifierimpedance, providing the appropriate voltage and current level shiftingand isolation if required. The transformation stage can be realized frompassive transformation networks, conventional transformers, wide-band ortransmission-line transformers, or similar means. An example of thistype of converter is formed by joining a Class-E inverter with a seriesloaded resonant rectifier, shown in FIG. 2. For this converter tooperate with high efficiency at VHF three primary loss mechanisms thatgrow with frequency must be overcome: switching loss due to the overlapof voltage and current at the switching instance and due to capacitivedischarge, gating loss due to charging and discharging the gatecapacitor once per cycle, and losses in magnetic materials. Switchinglosses are overcome by operating with zero-voltage switching (ZVS). Asshown in the waveforms of FIG. 3, the resonant components in the circuitare tuned specifically such that when the switch S₁ is opened, thevoltage across the switch (V_(D)(t)) will naturally ring up and thenback to zero at a known time period later, offering an opportunity toturn the switch back on with no penalty. With switching losses overcome,gating losses that arise from charging and discharging the gatecapacitor once per cycle are mitigated by either using a resonant gatedrive scheme to recover a portion of the energy stored in the gate,rather than discharging it to ground, or by optimizing the size of thetransistor such that gating loss is a small portion of the overallconverter loss. Finally, with switching and gating losses minimized,losses in magnetic materials are avoided by operating the converter at ahigh enough frequency such that high permeability core material can beeliminated and air-core magnetics or low-permeability RF magneticmaterials are used.

While the circuit of FIG. 2 overcomes all of the major frequencydependent loss mechanisms that prohibit conventional power convertercircuits from operation at VHF, it has a number of drawbacks. First, theswitch S₁ must survive a peak voltage stress of about 3.6 times theinput voltage. It is well known that increasing the breakdown voltage ofa transistor results in increased on-state resistance and increasedparasitic capacitance. The performance of converters of this type hasbeen shown to be directly related to the product of the on-stateresistance and device output capacitance squared. Thus, a topology withlower peak voltage stress will typically suffer less device loss.Second, the minimum output power is limited by the parasiticdrain-to-source capacitance of the switch S₁. Additionally, the circuitcan only operate with ZVS over a very narrow load range. Since thequality factor (Q) of the resonant components is set by the loadresistance, ZVS can only be obtained for a single load. As the loadchanges the circuit becomes de-tuned, and ZVS is lost. This effect isdemonstrated in FIG. 4, where the loss of ZVS is observed as the load isdecreased. Resistance compression networks, shown in FIG. 5, are amatching/transformation passive network that can be employed to reducethe sensitivity of the tuned inverter circuit to variations in the load.These drawbacks have led to the development of numerous other topologiesthat utilize higher-order resonant networks to reduce the peak voltagestress and break the tight coupling of output power and devicecapacitance. An example of such a topology is the Φ₂ converter, shown inFIG. 6

The Φ₂ uses a multi-resonant network to shape the voltage waveformacross the switch to approximate a square-wave with a peak value ofapproximately 2 times the input voltage, as shown in FIG. 7. This allowsa lower voltage transistor to be used, reducing device loss. Additionalresonant components are required, however, increasing the complexity(and potentially size) of the converter. In addition to the Φ₂ there arenumerous other converter topologies employing the similar strategy ofincreasing the circuit complexity to gain additional control over theshape of the converter waveforms. The Φ₂, however, is considered to bethe preferred embodiment as it strikes a good balance between additionalcomplexity and performance. While a resistance compression networkallows the converter to operate over a wide load range without loss ofZVS, it does not provide a means of regulation. Pulse-Width Modulation(PWM) is a commonly used technique for controlling power convertercircuits. However, PWM control at VHF is not practical since theconverters are designed to achieve ZVS at a particular duty cycle.Frequency modulation provides a method of control, however, it is achallenge to maintain high efficiency over a wide load range as lossesfrom gating and losses from providing the resonant currents required toachieve ZVS do not scale back with power.

A method that achieves high efficiency over a wide load range is on/offmodulation, shown in FIG. 8. This technique separates the functions ofenergy conversion and regulation by designing the converter to operateat full power, and then regulating average delivered power by modulatingthe converter on and off at a frequency less than the switchingfrequency of the converter. With this technique the resonant componentsof the converter are sized relative to the switching frequency and theinput and output filter components are sized relative to the modulationfrequency. Inclusion of a resistance compression network with aconverter that is controlled through on/off modulation increases theinput and output voltage range of the converter.

While the rectifier stage of FIG. 1 is classically realized usingdiodes, transistors can also be used to build a synchronous rectifier.Replacing an uncontrolled switch with a controlled switch adds therequirement of knowing the correct times to turn the switch on and offwithin a cycle. This is demonstrated in FIG. 9 by varying the inputvoltage of the converter of FIG. 2 and observing that the rectifier'sduty cycle and phase vary relative to the inverter. All of thesoft-switched resonant inverter topologies previously introduced have adual circuit that operates as a rectifier. FIGS. 10 and 11 showschematics of both the Class-E and Φ₂ inverters connected to theirrespective rectifier dual circuit. In these examples the transformationnetwork is only a simple impedance, but just as with converters builtwith diode rectifiers, more complex passive transformation networks,conventional transformers, wide-band or transmission-line transformers,or similar means can also be used.

When designing a synchronous rectifier in a converter that is controlledthrough on/off modulation, the primary task is to control the duty cycleof the rectifier and inverter switches as well as the phase shiftbetween the inverter and rectifier to achieve the desired switchingwaveform. This may be accomplished through the following method:

1. Determine the duty cycle for the inverter and rectifier switches aswell as the phase shift between the inverter and rectifier as a functionof input and output voltage that results with the desired switchingwaveforms. Since ZVS is not necessarily obtainable for all combinationsof input and output voltage, the desired waveforms are chosen tominimize converter loss and/or damage to the converter for the caseswhen ZVS cannot be obtained. Depending on the converter topology usedthis can be done using different methods. Converters for which closedfor solutions describe their operation the duty cycles and phase shiftcan be determined from analysis of the equations. If no such set ofequations exist for the topology simulation sweeps across parameters orthrough a numerical converter solution.

2. With the desired duty cycles and phase shift known as a function ofinput and output voltage, the remaining task is to realize a practicalsystem that implements the desired transfer functions. One method toaccomplish this is to read the input and output voltage at a bandwidthless than the switching frequency. This ensures that the duty cycles andphase are being adjusted with the DC input and output voltages, wherethe term DC loosely is meant to mean slowly varying local averagerelative to a switching cycle.

3. Using the measured local average input and output voltages, the dutycycle of the inverter and rectifier circuits are set as well as thephase shift between the inverter and rectifier. Synchronous rectifierscan also be used to implement a phase-shift control system in which inaddition to ensuring the converter operates with the desired switchingwaveforms, regulation is also controlled through adjustment of the phaseshift between the inverter and rectifier.

Building VHF power converters where the main switching devices arefabricated in an integrated power process typically limits the selectionof suitable devices to those having a breakdown voltage of 80-100 Voltsat most. Since the best designed resonant converters of this type have apeak voltage stress of 2 times the input voltage in the inverter and 2times the output voltage in the rectifier, the input and output voltagesare both constrained to being less than 50 Volts at most. Manyapplications exist that require higher input or output voltage, however.For example, a system that is powered directly from the AC line musthandle a peak input voltage of about 190 Volts and a peak device stressof 380 Volts, forcing the converter to be built from either poorlyintegrated devices or external devices. Here we describe a method andsystem of extending the peak input and/or output voltage of a VHFresonant DC/DC converter without requiring devices with a higherbreakdown voltage. Rather than using a single converter cell, theconverter can be built from multiple converter cells, and peak voltageis extended by connecting the converters in series. It is not necessarythat both the converter's input and output both be series connected, butrather as shown in FIG. 12 the cells' inputs can be connect in seriesand their output is parallel, such as to extend peak input voltage.Similarly, to increase the peak output voltage of the converter only,the cells' outputs can be connected in series and the inputs inparallel. Additionally, some combination of series and parallel can beutilized at the input and/or output to achieve a particular peak voltageand power. It is further envisioned that sets of series stackedinverters may be configured in parallel (e.g. parallel outputs) forproviding greater power than could be provided by a single series stack.A determination of which type of configuration may be based on arequirement to deliver a required amount of output power. Configuringseries stacked inverters in parallel may be an arrangement thatsatisfies the output power delivery requirement.

The cells used to form the multi-cell converter will be described hereinand may vary depending on a variety of factors including size, cost,performance objectives, input voltage range limit, and the like. Inaddition to increasing the converter's peak input and/or output voltagefor a particular device breakdown voltage, the range at which theconverter can operate over can also be increased. This may beaccomplished by selectively using only a subset of the cells that makeup the multi-cell converter. For example, if a multi-cell converter isformed from 5 converter cells that can each operate over an inputvoltage range of 20-30 Volts, with all cells in use, the multi-cellconverter can operate over a voltage range of 100 Volts-150 Volts.However, by selectively using a subset of the cells in the series stack,the multi-cell converter can operate over an input voltage range of20-150 Volts. A multi-cell converter may additionally include controlfunctionality for each cell so that active cells remain within theirinput and output voltage range.

In the present disclosure some embodiments of a VHF converter aredescribed as including VHF soft-switching resonant DC/DC converterstages that are cascaded with an AC bridge to form an AC/DC converterthat can operate efficiently with a VHF switching frequency. This AC/DCconverter may be used to drive light emitting diodes as well as spaceconstrained consumer devices, such as an AC/DC converter used to power alaptop computer, and the like.

A block diagram of two similar embodiments of such a VHF convertersystem is presented in FIG. 13. Embodiment VHF1302 includes energystorage, whereas embodiment VHF1304 does not. The DC/DC converter stagesVHF1308 may be operated with a switching frequency that is much greaterthan the line frequency so that the line voltages appears to the DC/DCconverter VHF1308 to be a widely but slowly varying DC voltage. Thestages VHF1308 may be formed from any of the previously described VHFresonant DC/DC converter cells and/or multi-cell configurations,including combinations thereof.

The input voltage range of the stage may determine which portion of theline cycle that the stage is able to operate over. For a portion of theline cycle where the line voltage is below the minimum input operationvoltage of the stage, energy storage may be required to maintain theoutput voltage or output current to within any ripple limits specifiedby a particular application system. Additionally, in many applications,the method in which power is drawn from the AC line is constrained bygovernment standards. This may further reduce the ability of the stageto regulate the output voltage or current to within the specified ripplelimits. Although one option to maintain output ripple to within itslimits is to increase the energy storage buffer at the output, this mayreduce the flexibility and increase the complexity.

An alternative solution is to cascade a second DC/DC converter stagewith energy storage to perform load regulation and ripple reduction.This allows the amount of energy stored to ripple widely within a linecycle, thereby reducing the total amount of energy storage requiredwhich may reduce complexity, overall size, and cost.

A very high frequency power converter suitable for implementation in asemiconductor process that overcomes size, efficiency, and costlimitations of larger discrete component embodiments is describedherein. The VHF power converter may be configured to deliver substantialbenefits of high frequency operation while providing power output thatis far greater than may have economically been provided by VHF convertertechnology heretofore. The VHF power converter may take advantage of aswitched stacked cell architecture that enables the converter to acceptan input voltage far greater than could be tolerated by any single cellwhile achieving performance, cost, size, and efficiency levels affordedby the current VHF power converter as described herein.

A VHF power converter may include a core cell architecture that mayinclude a switched capacitor stage followed by a switched VHF converterstage. A switched capacitor stage may facilitate each cell accepting awider range of input voltage by providing a controllable voltage halvingfunction. By employing one or more switched capacitors, each capacitorcan be charged up to one-half of the input voltage by alternatingcapacitor charging with capacitor discharging. Therefore, an inputvoltage to a cell of 60V may be divided in half to 30 V through theswitched capacitor stage. The number of switched capacitors may bedependent on a variety of factors such as reduced input current, and thelike. The output of the switched capacitor stage may be provided to aVHF power converter stage so that the VHF converter stage receives nomore than 30V. This concept may be further enhanced by providing aswitched direct path from the input to the VHF converter to supportinput voltages that do not exceed 30V and therefore do not necessarilybenefit from being divided in half by the switched capacitor stage. Inan example, a switched capacitor-based VHF converter cell may accept aninput voltage from 15V to 60V while never presenting more than 30V tothe VHF stage.

When a VHF converter is configured with a plurality of switched cells,such as the capacitor stage plus VHF stage cells describe above areconfigured in series across an input, an input voltage to the convertermay range from as little as a minimum required for VHF conversion in asingle cell to a maximum determined by the number of cells. In anexample, a VHF converter using four of the switched capacitor stage plusVHF stage described above may support an input range of 15V minimum toas much as 240V maximum peak.

An exemplary embodiment of a switched cell based on a switched capacitorstage followed by a VHF stage is depicted in FIG. 14. This exemplarycell architecture may comprise a pair of switched capacitor chargingcircuits 1402 and 1404 wherein energy in each capacitor may be providedto a VHF stage 110 via a VHF stage input switch 1408. Each capacitorcircuit, such as 1402 may comprise four series switching transistors anda capacitor connected between a junction of the top two series switchesand the bottom two series switches. The capacitor may be alternativelycharged and discharged by operating the switches in two phases. In thefirst phase the top switch and the switch just below the midpoint areclosed and the remaining two switches are open. In this phase, energydrawn by the VHF stage 1410 through input switch 1408 charges thecapacitor. In the second phase, the state of each switch is reversed,and the energy drawn by the VHF stage 1410 through input switch 1408discharges the capacitor. With the VHF stage 1410 drawing substantiallythe same energy in both phases, the switched capacitor circuit presentsa voltage half of the cell input voltage 1412 to the VHF stage 1410through input switch 1408. Switched capacitor charging circuit 1404operates similarly to switched capacitor charging circuit 1402. Switchedcapacitor charging circuits 1402 and 1404 may be operated cooperativelywith opposite phase to reduce the RMS current stress of the converter.The example of FIG. 14 includes two switched capacitor chargingcircuits; however any practical number of capacitor charging circuits orswitch configurations may be used, such as to facilitate different cellinput voltages 1412, make system efficiency tradeoffs, and the like.

VHF stage input switch 1408 may comprise a pair of switches connected inseries between the cell input voltage 1412 and the center point of eachswitch capacitor charging circuit 1402 and 1404. The joining point ofthe two switches may be an input point to a VHF stage 1410. VHF stageinput switch 1408 may facilitate selecting either cell input 1412 orvoltage from switched capacitor converter as an input to the VHF stage1410. If both switches in VHF stage input switch 1408 are off/open, nopower will be input to the VHF stage 1410. Control of the two switchedcapacitor circuits 1402 and 1404 along with the VHF stage input switch1408 may be coordinated to ensure that VHF stage 1410 receives a voltagethat is sufficient for operation but does not exceed a safe operatingvoltage by controlling the charging of capacitors 1402 and 1404 andselecting between the power sources provided to VHF stage input switch1408. In an example of steady state operation of the cell depicted inFIG. 14 with an AC cell input voltage 1412, VHF stage input switch 1408may connect the VHF stage 1410 to the cell input voltage 1412 while thecell input voltage 1412 is within the input voltage range of the VHFstage 1410. Further more, stage input switch 1408 may connect theswitched capacitor circuits as a source of power to the VHF stage 1410while the switched capacitor output voltage in within the input voltagerange of the VHF stage 1410. One example of selecting the cell inputvoltage to directly energize the VHF stage 1410 may include aconfiguration in which the cell input voltage is a DC voltage within thesafe operating input range of the VHF stage 1410.

An exemplary embodiment of a serial stacked cell VHF converter isdepicted in FIG. 15. The embodiment of FIG. 15 includes four switchedVHF cells that are arranged in pairs to drive a load through transformerisolation. The four switched VHF cells work cooperatively to handle arectified AC line voltage up to 120 VAC. Each of the cells has at leastone specific function that is activated based on the input voltage.Cells 1 and 2 provide an output power regulation throughout the fullline cycle. Cell 3 is bypassed until the input reaches approximately125V above which it provides input voltage regulation across cells 3 and4. Cell 4 is off until the input reaches approximately 80V above whichit provides input current regulation for the entire stack.

FIG. 16 provides a timeline view of one rectified cycle of an 137.5 VACinput that helps one visualize the portions of the cycle for which eachof the four cells performs its at least one specific function. In FIG.16, the cycle is divided into five voltage zones rising 0-80V, rising80-125V, rising and falling above 125V, falling 125-80V, and falling80-0V. As noted above cells 1 and 2 provide an output power regulationfunction throughout the cycle. During the rising 0-80V zone and duringthe falling 80-0V zone cell 3 is bypassed and cell 4 is off. Duringrising 80-125V and falling 125-80V zones, cell 3 is bypassed and cell 4regulates input current. During the rising and falling above 125V zonecell 3 is activated to regulate input voltage across cells 3 and 4, cell4 continues to regulate input current, and cells 1 and 2 continue toregulate output power. Also depicted in the timeline of FIG. 16 are thetypical voltages present on each cell represented by V1 for cell 1, V2for cell 2, V3 for cell 3, and V4 for cell 4. The cells are controlled(switched) so that at no time is a voltage across any one cell greaterthan 60V.

Referring back to FIG. 15, in addition to the four switched cells thatare arranged in pairs, each pair drives the load through multipleprimary windings of a transformer. Because the embodiment of FIG. 15includes four cells arranged in two groups, two transformers aredepicted. Although the embodiment of FIG. 15 depicts pairs of cellsconnected through a single transformer with multiple primary windings,an alternate embodiment could include other arrangements, such as aseparate transformer for each cell. Although other types of isolationare possible (e.g. capacitive), transformer isolation also may providebenefits, such as facilitating storage of converter energy. Therefore,as depicted in FIG. 15, a VHF switched power converter may be configuredto deliver power through a transformer connected to outputs of multipleswitched cells through multiple primary transformer windings. Also, aplurality of such configured multiple switched cell to transformercircuits may be configured substantially in parallel to drive a load,such as an LED-based light. The embodiment of FIG. 15 further depictscontrolling each switched cell separately while coordinating control ofeach cell within a designated pair to facilitate achieving variousfunctional and/or performance objectives and/or coordinating control ofeach of the pairs of cells to achieve various functional and/orperformance objectives as described herein and otherwise understood byone knowledgeable in the state of the art.

The embodiment depicted in FIG. 15 also facilitates power factorcorrection through at least the use of capacitor designated as CPFC andat least through the control of cell 3. Power factor may be corrected bycontrolling cell 3 in FIG. 15 so that capacitor CPFC charges anddischarges throughout the power AC line cycle. In the AC line cycleportion depicted in FIG. 16, capacitor CPFC discharges during rising0-80V and during falling 80-0V portions. Capacitor CPFC charges duringrising and falling above 80V portions of the cycle.

Selected thresholds shown in FIG. 16 are representative only and may beadjusted based on the fabrication technology chosen for the cells, thenumber of cells, the frequency of switching, the output power, thecapacitance value of CPFC, and various other design choices that mayimpact such thresholds.

Each cell in the stacked-cell configuration of FIG. 15 may requirecontrol bandwidth that facilitates proper control of each cellthroughout an AC cycle. In an example wherein harmonics within thesystem are generally 1 kHz, cell 1 may be controlled at a 1 MHz rate,cells 2 and 3 at a 100 kHz rate, and cell 4 at a 10 kHz rate. Thisdifference in control frequency may enable control for high efficiency,accurate cell voltage balancing, and the like.

The embodiment of FIG. 15 further includes an overvoltage protectioncircuit 1504 to facilitate protecting the VHF converter circuits fromvoltage spikes, overvoltage conditions, and the like. The protectioncircuit 1504 may be controlled so that input voltages to the converterand/or to any element or group of elements of the converter that exceeda maximum safe operating threshold may be limited by the protectioncircuit 1504 to avoid damage or overstress thereto.

In applications of the VHF power converter of FIG. 15 for driving alight, such as an LED-based light, dimming, such as by a phase-cuttingline input switch (e.g. Triac for conventional incandescent bulbdimming), may be accommodated by the VHF power converter. For reliablephase-cut dimming, a minimum load may be required to be presented to thephase-cut dimmer throughout the phase-cut dimming function. This may beaccomplished by controlling the VHF converter to present a low impedancewhen the phase-cut dimmer is blocking the AC line voltage through switch1502 controlled by cell 3 in FIG. 15 and controlling the VHF converterto maintain a minimum holding current when the phase-cut dimmer passingthe AC line voltage during the dimming function.

One approach to operate the VHF converter with a phase-cut dimmer forlight dimming is for the VHF converter to detect the AC line conductionangle and adjust capacitor charging and output current accordingly. InLED-based lighting applications, the minimum holding current required bythe phase-cut dimmer may be greater than the current required to powerthe LED. In this scenario, cells 1 and 2 in FIG. 15 may be controlled toregulate the output, cells 3 and 4 in FIG. 15 may be controlled to drawthe required holding current and deliver no output power, and switch1502 in FIG. 15 may be controlled to charge CPFC to the desired value tomaintain the output power while the phase-cut dimmer is blocking the ACline voltage. By adjusting the control scheme based on conduction angle,dimming with a VHF power converter can be accomplished without addingcomponents that are dedicated to the dimming function. This reducesfootprint and costs of such a VHF solution over other multi-componentdimming solutions.

VHF converters, and in particular multiple cell VHF converters maybenefit from precise clock synchronization among the cells. Whenmultiple cells share an output rectifier (as depicted in FIG. 15 forcells 1/3 and 2/4), clocks of the rectifier-paired cells may besynchronized. Generally cell to cell clock skew of 500 ps or greater mayresult in reduction in efficiency due to energy losses when operating atVHF frequencies. Although cells may be implemented within a singleintegrated circuit, some applications may demand separation of cells todistinct integrated circuits that are connected by printed circuit boardtraces and/or through additional components which may introduceadditional skew. To accommodate precise synchronization of cellclocking, a reference clock may be provided throughout the VHF circuittopology that can be used to adjust for circuit related frequency skew.In addition, clock phase skew may be detected from analyzing fluxgenerated by cell switching and transformer coupling with peak and hillclimbing algorithms because phase skewed clocks may produce flux peaksthat could be determined from such analysis. Clocks to the cells can beadjusted based on the detected peak analysis with the objective ofimproving cell to cell clock synchronization which may be determined bydetecting a single flux peak. In embodiments in which cells do not sharea rectifier stage, demand for cell-to-cell clock synchronization may bereduced.

Clock frequency accuracy (e.g. repeatability) that may also be importantfor highly efficient VHF conversion may be accomplished by use of ZeroVoltage Sensing (ZVS) sensors that may facilitate accurate clockswithout the use of a crystal oscillator, a complex calibrationarchitecture, and the like. By taking a snapshot of an amplitude(voltage) of an input of one or more of the switched circuits an instantbefore the circuit is switched one can determine if the switch clock isoccurring precisely as desired (e.g. when the input voltage is zero).The snapshot voltage may be used to control a phase-lock loop or thelike to adjust the clock frequency as desired. In an application inwhich an AC line signal is used as an input to the VHF converter, theclock may initially be synchronized to the AC line input. This mayfacilitate effective use of a phase-lock loop by configuring thephase-lock loop to track the zero voltage crossing of the AC line inputthat is generally controlled to within approximately 10 percent. Oncethe clock frequency is locked to the a multiple of the AC linefrequency, the converter can begin to run, and the ZVS sensors may beused to further set the clock frequency. The techniques for clock periodadjustment and/or clock synchronization as described herein may furtherbe used to overcome variations in manufacturing process andtemperature-based drift that may impact clock related issues withoutrequiring extensive production or test time calibration.

In VHF converter configurations that include a synchronous rectifierstage, maintaining a particular phase angle for the synchronousrectification may provide benefits including efficient and accurateoperation of the conversion function. Detection and control of the phaseangle of a synchronous rectifier may be implemented in a VHF converterthrough phase angle sensing and processing techniques, such as throughthe use of a delay locked loop, and the like. Phase angle control ofsynchronous rectification may include average feed forward sensing, zerovoltage detection feedback, average sensing, duty ratio/clockfrequency/phase angle adjustment based on sensed voltage changes, andthe like.

A multi-cell VHF converter, such as based on the switched stacked cellconverter architecture depicted in FIG. 15 may include control tofacilitate cooperative operation of the cells and related components toachieve various functional and performance objectives, such as clocksynchronization and others. Control may further be based on any of avariety of parameters including feedback associated with converting aninput to an output voltage, predetermined parameters, learnedparameters, user provided parameters, and the like. Control may beprovided by a controller, such as logic, state machines,microcontrollers, and the like. FIG. 18 depicts a block diagram of a VHFpower converter that includes control. A controller may facilitatecontrol of the VHF converter to achieve a degree of constant inputcurrent, constant output current, and cell control based on aspect of aninput voltage such as an AC line voltage.

Control may be based on a plurality of control loops a portion of whichmay be nested. In one embodiment of the VHF converter for powering anLED-based light, control may include at least two control loops—an outerloop and an inner loop that operates at a faster cycle time than anouter loop and that may implement proportional feedback to directlycontrol each aspect of the VHF converter (e.g. cell clocks, feedbacksampler, and the like). The outer slower loop may facilitate providinginput to the inner loop when the inner loop is controlling the VHFconverter to maintain a constant input current. The outer loop mayfacilitate detection and feedback of an average of the output current toensure that an average of the output current is also controlled. Theouter loop may first integrate the difference between an instantaneousoutput current and an output current reference (e.g. an average of theoutput current from a previous AC line cycle). This integral is thenprocessed to generate a reference value for the inner loop.

Any number of control loops that may be required may be implemented in acontroller, such as depicted in FIG. 17. Generally a VHF converter iscontrolled to maintain at least one of a desired input current and adesired output current. However, control of both input and outputcurrents may be required to ensure high efficiency VHF conversion, tomanage thermal impact, to perform power-factor correction, and the like.In another embodiment, a controller may include control for dimming,line voltage variation (normal cycle and exceptional variation), VHFconverter start-up mode, steady state mode, line transient, and thelike. Startup mode may be controlled to facilitate avoiding damage tothe cells as power to the VHF converter turns on. Steady state mode maybe controlled to facilitate efficient, high quality power conversion;Line transient or over-voltage may be controlled to facilitateprotection of the converter cells and other devices, such as with theprotection circuit 1704 described herein. Dimming may require controlfor operation of a phase-cut dimer, and the like as described herein.

Referring to FIG. 17, an input current control loop and an outputcurrent control loop are depicted. As noted in the description of FIG.15, cells 1 and 2 primarily control output current and cells 3 and 4primarily control input current. The flow diagram of FIG. 17 provides avisualization of control flow with respect to both input and outputcurrent. Input current (A) and output current (B) may be combined toprovide feedback for power balance 1702 which may impact an inputcurrent reference 1704.

An input current control loop may include input current reference 1704and filtered input current 1708 may be combined and processed, such asthrough compensator 1710, to impact control of cells 3 and 4 1712.

An output current control loop may include an output reference 1714 andfiltered output current 1718 that may be combined and processed, such asthrough compensator 1720 to impact control of cells 1 and 2 1722. Outputcurrent control may further include combining sensed portions of inputcurrent (E) and sensed portions of cells 1 and 2 1722.

The cells of the converter are modulated on and off as a primary meansfor providing control of the input current, output current and voltage,and the like. In FIG. 18, a PWM block provides pulse width modulationcontrol of the various cells, the power core, and the like. The PWMblock may also provide overall PWM control of the converter output toenable pulse-width modulation of the output voltage or current presentedto a load, such as to an LED-based light. This may be helpful inapplications in which PWM operation of an LED-based light may facilitateadjusting color of an LED string, brightness of the LED, and the like.PWM control of the output may facilitate dimming an LED-based light inresponse to the converter input being controlled by a conventionalphase-cut dimmer.

As described herein, control of a VHF converter, such as an AC to DCconverter, a VHF stacked cell, soft switched converter, and the like maybe based on input voltage requirements, output voltage requirements,instantaneous input voltage, average output voltage, and the like. In anAC-DC VHF converter, stack control varies throughout the AC cycle asdescribed above in regards to FIG. 15 and FIG. 16. As noted above acontrol loop, such as may be executed by a controller, may beresponsible for adjusting the number of active cells because the numbermay vary with the amplitude of the input voltage and/or the direction ofthe amplitude (rising or falling). Generally control may attempt toensure that the active number of cells is proportional to a measure ofinput voltage. Activating (adding/turning on) a cell may be appropriateas input voltage rises. Deactivating (turning off/bypassing/removing) acell may be appropriate as voltage decreases. Control may include a cellbypass function that may switch in/out cells from the active stack ofcells to achieve certain objectives. In an example, opening a cellbypass switch as the input voltage increases may enable support forgreater input voltages. In another example, closing a cell bypass switchas the input voltage decreases may maintain efficiency and facilitatestaying within an operating range of the stacked cells.

Control of the various functions, cells, switches, and the like of theVHF converter may be provided by a communications channel among theelements. The communication channel may be an asynchronous bus that maybe implemented as any type of physical bus. The communication channelmay be an isolated. Examples include a level shifting bus, a digitalbus, capacitive coupling, magnetic coupling, optical coupling, and thelike. The communication channel infrastructure may include individuallyaddressable cells and subsystems on and among circuits in the converter.Messaging over the communication channel may include high/low prioritymessages, broadcast messages, single listener messages, and the like.

Referring to FIG. 19, an embodiment of the inventive VHF power convertersystem described herein that may be suitable for use in MR16 typelighting power applications, some additional control-related techniquesare depicted. In addition to PWM, control, input and output sensing, andthe like, characteristics of any of the inverters and/or of thesynchronous rectifier may be sensed and used in control, such as tocontrol clock phase, skew, zero voltage switching, and the like. In theembodiment of FIG. 19, waveform characteristics for an inverter denotedas DI and/or waveform characteristics of a synchronous rectifier denotedas DR may be sensed, compared to a threshold, and provided to clockcontrol logic for use in controlling clocks to individual cells, to gatedrivers, and the like. Sensing DI and/or DR may enable dynamic controlof clock related aspects to facilitate compensating for manufacturingvariations, temperature drift, and the like. FIG. 19 also depictsvarious other control inputs including sampling the VHF converter inputvoltage that may be optionally divided by divider 1902 to support fullAC line voltages, input current sensing 1904, output current sensing1908, controller state/input sensing 1910, and the like.

Powering switch drive gates in a VHF power converter may require asubstantial amount of drive energy (e.g. hundreds of milliwatts). In asemiconductor process, a switch drive gate may need to be driven in therange of 0-3 volts, yet a typical VHF power converter may receive asmuch as 120 VAC input. Therefore, converting a rectified AC line to the3 volts required for driving a switch drive gate can be costly in realestate, heat, efficiency, or the like. In addition to requiring a powersource for the switch drive gates, digital logic for a VHF powerconverter also needs a continuous source of power to keep the digitallogic functioning properly to control the VHF power converter forexample. To provide the continuous power for digital logic and/or forswitch drive gate operation, an auxiliary source of power may beprovided. This auxiliary power may be provided by a dedicated VHFconverter circuit that converts a main power close to the requiredvoltage.

An embodiment of a dedicated VHF converter for auxiliary power may bedesigned to overcome many of the drawbacks noted above while providing acontinuous source of power. Such an embodiment may function in twocontrolled power phases (i) using the main VHF power input for chargingan auxiliary power capacitor that provides energy storage to driveauxiliary power loads (sending energy to the auxiliary power subsystem),and (ii) discharging the auxiliary power capacitor to generate powerthat can be provided back to the main VHF converter that provides powerto the main load (sending electrical energy from the auxiliary powersubsystem to the main power converter system). A ratio of time drivingpower to the auxiliary power subsystem versus time driving power fromthe auxiliary power system to the primary VHF converter system maydetermine the average auxiliary power provided. Switching betweendriving power into the auxiliary power system and driving power out ofthe auxiliary power system may be adjusted (phase, duty cycle, and thelike) to manage average auxiliary power consumption. A dedicated VHFconverter configured as described herein for providing auxiliary powermay be much more efficient than a linear regulator and much smaller thana Buck-type converter.

Operation of a dedicated Auxiliary power converter may includealternating between a first phase that rectifies AC power generated froma portion of a main VHF converter stage (e.g. an inverter) and providesthe rectified power to an auxiliary output for use and storage therebyand a second phase that generates AC power from the stored auxiliarypower and provides the generated AC power to the main VHF converter.

Such a bi-phase auxiliary power circuit is depicted in FIG. 20. First tofacilitate proper operation during initial power-up (e.g. before theauxiliary power VHF rectifier is a reliable power source), a linearregulator circuit 2002 may be included to power circuits duringpower-up. Once the converter control logic and power circuits arestable, the linear regulator may be disabled via linear regulatormonitor 2004 to reduce overall power consumption.

Energy transfer direction may be controlled by selecting a clock source2008 for the auxiliary power dedicated converter. CLKFWD and CLKREV mayclock the auxiliary VHF converter at different phases of the AC cycle toresult in energy being transferred to auxiliary power capacitor 2010when clocked by CLKFWD. When clocked by CLKREV, energy may be reversedfrom capacitor 2010. Auxiliary power VDD may be maintained during CLREVoperation by the energy stored in capacitor 2010.

Power-Factor Correction (PFC) is a power conversion technique thatlimits the amount of reactive power drawn from a source. High powerfactor, which is defined as the ratio of real to apparent power, isachieved by controlling the current that is drawn from a source suchthat the load appears to be substantially resistive. PFC is oftenemployed in devices that are connected to the AC main as reactive powerunnecessarily loads the AC grid. FIG. 21 shows the waveform of arectified AC voltage with a current waveform that achieves unitypower-factor. From this figure it is readily observed that a keylimitation and challenge faced by AC/DC PFC converters is the necessityto buffer energy at twice the AC line frequency as the power drawn fromthe AC source reduces to zero twice per cycle.

An energy buffer may be required to maintain the DC output power whilethe input power drops to zero. This energy buffer is often realized as acapacitor. A simple method of implementing the buffer is to include acapacitor at the output of single-stage PFC converter. An arbitrarilysmall output ripple can be obtained by increasing the size of thiscapacitor. However, in many space-constrained applications this can beprohibitive as the volume occupied by the capacitor can be quite large.

For a given output power, the size of the energy buffer capacitor may bereduced if its voltage is allowed to ripple as a function of the linepower. However, this method is incompatible with the simple single-stagePFC solution described previously. In that solution the capacitor isconnected directly across the output and the load ripple voltage andcapacitor ripple voltage are identical. Since most loads require astable DC output with very small ripple, a second converter may becascaded in series with the first to remove the ripple from the outputas was shown in FIG. 13. In such a configuration, the output port of thefirst converter is attached to the input port of the second converterand this common port is also shared by the capacitor. This allows a pureDC output to be obtained while the capacitor voltage is rippling, butefficiency suffers owing to the system efficiency being the product ofthe efficiencies of each stage.

Yet another approach to reduce the capacitor size involves a singlestage AC/DC converter with the energy storage capacitor located at theinput. This allows a much smaller total capacitance because the energyis buffered at line voltage and the total energy stored in a capacitoris proportional to its terminal voltage squared. This solves the problemof poor efficiency experienced with two-stage converters while alsoallowing for a small capacitance. However, existing examples of thisapproach have poor power factor (typically 0.5 or less) because thecapacitor contributes a current component that is orthogonal to therectified line voltage.

Herein we describe an AC/DC PFC converter architecture that achieves afully-regulated DC output with arbitrarily small ripple, highefficiency, and high power factor with use of a small energy storagecapacitor. The architecture uses a plurality of converter cellsconnected to provide multiple single-converter-cell paths from thesource to the load. This allows for high efficiency while providingcontrol over the current drawn by an energy storage capacitor connectedto the input side of the converter cells such that the system has highpower factor. This capacitor can store energy at a relatively highvoltage and with substantial ripple enabling it to be very small. Theresulting converter, fully described below, is a significant advanceover state-of-the-art PFC converter technology.

FIG. 22 presents a block diagram that illustrates one implementation ofthe power factor correction methods and systems of this disclosure. Thisimplementation operates with two paths for energy transfer to the loadthat are series connected across the rectified AC source and parallelconnected across the load. This implementation also includes acapacitive energy storage network in parallel with the input to one ofthe energy transfer paths. The energy transfer paths are controlled suchthat a fraction of the energy drawn from the AC source is delivered tothe load, and the remaining fraction of the energy is delivered to thecapacitor. As shown in FIG. 22, the input voltage of energy transferpath 1 (V1) is equal to the rectified AC voltage (VLINE) minus thecapacitor voltage (VC). Since Path 1 is in series with the rectifier,the power that is drawn by this path sets the current that is drawn fromthe AC source (ILINE). The capacitor current (IC) is set by thedifference between the ILINE current and the current drawn by energytransfer path 2 (I2). This allows the ratio of power delivered to theload and power delivered to the capacitor to be controlled.

One method to perform AC/DC PFC with this architecture is to controlPath 1 to draw the desired PFC current waveform from the AC source.Since the voltage V1 is set by the difference between VLINE and VC, Path1 is unable to perform PFC by controlling the input current andsimultaneously regulate the output. However, if over the entire linecycle the instantaneous power drawn by Path 1 is no more than the DCoutput power delivered to the load, Path 2 can be used to regulate thepower delivered to the load by supplying the difference between the DCoutput power and the power delivered by Path 1 . The difference inenergy (e.g. an instantaneous difference) between what is drawn from theAC line and what is delivered to the load is naturally sourced or sunkby the capacitor.

FIG. 23 presents simulated waveforms over a single AC line cycle for thePFC implementation of FIG. 22. Energy transfer path 1 begins conductingwhen VLINE rises above VC. A pure DC output can be obtained if the sumof P1 and P2 is equal to average power drawn from the AC source. Thiscondition is met if

$V_{C} \geq {V_{LINE} - \frac{P_{AVG}}{I_{LINE}}}$while Path 1 is conducting. The capacitance must be chosen such that thecapacitor voltage does not violate this relationship. Path 1 ceasesconduction when VLINE drops below VC. Path 2 then discharges thecapacitor to maintain the DC output power until VLINE rises above VC inthe next half line cycle, at which point the cycle repeats.

With this configuration, unity power factor might not be obtained sincecurrent might not be drawn from the AC source throughout the entire linecycle (i.e. the portion where VC is greater than VLINE). While unitypower factor might not be obtained, the waveforms of FIG. 23 achieve apower factor greater than 0.95 which is sufficient for manyapplications.

One method to implement each energy transfer path is through the use ofa high frequency switched-mode power supply (SMPS) (e.g. with aswitching frequency that is greater than 1 MHz, for example). On/offcontrol can be used to obtain the desired average output of each SMPS tosupply the load.

A second implementation of power factor correction includes a switchnetwork in addition to the previously described implementation such thatunity power factor may be obtained. FIG. 24 presents a block diagram ofthe implementation. The switch network, labeled S1 in FIG. 24, isutilized to enable energy transfer path 1 to conduct current (e.g.control ILINE) throughout the entire AC cycle. In the portion of the ACcycle for which VC is greater than VLINE, the switch S1 is used tobypass the capacitor and energy transfer path 2, such that the voltageacross the input of Path 1 is not driven negative. This enables Path 1to conduct current throughout the entire line cycle and unity powerfactor may be achieved. FIG. 25 presents sample waveforms over acomplete AC cycle for this implementation. Since Path 1 is enabled tocontrol ILINE throughout the entire line cycle, unity power factor isachievable. Furthermore, this implementation has an advantage when usedin applications in which the frequency components of ILINE areconstrained since ILINE is controlled throughout the entire AC cycle.

It will be appreciated that there are a range of variants to the PFCarchitecture discussed herein that fall within the scope of thisdisclosure. For example, it is not necessary that the current drawn fromthe AC source be substantially sinusoidal. In many applications it isacceptable to draw current from the AC source that contains frequencycomponents in addition to the fundamental. In FIG. 26 an example currentwaveform is presented that contains odd harmonics in addition to thefundamental. The current waveform has a shape that may not peak at thesame time as the AC voltage within an AC cycle. As a result, the peakminimum capacitor voltage for maintaining a pure DC output may bereduced. With this reduced peak, a smaller capacitance can be usedbecause VC may ripple over a wider range without violating the minimum.

Furthermore, while the exemplary embodiments have described a pure DCoutput, a time varying output (e.g. AC) can be utilized withoutdeparting from the scope of the disclosure. For example, allowing theoutput to ripple with a fundamental frequency equal to that of the ACsource reduces the size of the capacitor required. Additionally, in manyapplications it is desirable to control the output to an average value,such as through on/off modulation. One such application is driving oneor more LEDs for illumination or other applications where it isdesirable to achieve a consistent set of light emission characteristicsas the power delivered to the LEDs is varied. This may be accomplishedby driving the LEDs at a particular instantaneous power level, and thencontrolling average power through on/off modulation of the LEDs (e.g.such as with high frequency switched-mode power supplies as describedherein). Implementing this with multiple paths for energy transfer tothe output may be accomplished by the energy transfer paths beingcontrolled such that when any subset of paths is conducting the load isdelivered a constant output power. One way this can be accomplished isto interleave the on-time of each subset of the energy transfer paths.As a result, each subset may deliver the desired instantaneous outputpower, and only a single subset may be delivering power at a particularinstant of time.

The previously described implementations include the use of two energytransfer paths and a capacitive energy storage network. The scope hereofincludes the generalization of this technique to a plurality of pathsfor energy transfer to the output, where the energy transfer paths arecontrolled to deliver a fraction of the energy to a capacitive energystorage network, and a fraction of the energy to the load.

Many electronic systems require multiple regulated output voltages orcurrents derived from a single input source. For instance, in a cellulartelephone there are typically multiple buss voltages—a logic corevoltage, an intermediate voltage for interface, and a third that is usedfor the RF power amplifier. Some phones may require a high voltage orpower output for driving LED camera flashes or displays, as well. Manycomplex systems have similar requirements. Often these are met by usinga multitude of independent regulators, whether linear or switch-mode,where each produces one of the desired outputs.

Another common realization of multiple outputs is a single converter,such as a switch-mode power supply (SMPS), with multiple taps on atransformer or inductor winding. Each point on the winding can be usedto provide a desired output voltage relative to a single regulatedvoltage. This has the benefit of reducing the overall complexity (andtypically, size) of the system, but only permits the regulation of oneoutput voltage. The others are subject to variations introduced byAC-side reactance, such as transformer leakage inductances that make theoutput voltage a function of the load current.

Regulation of each tap in a multiple-output converter as described abovemay be accomplished (where required) by means of linear post regulationstages. A low-dropout, linear regulator (LDO) is inserted between a tapand provides compensation for the droop that normally occurs. This iseffective, but requires the addition of an LDO for each desired output(excepting the one that is already regulated), adding cost andcomplexity to the system. It also reduces efficiency, as some minimumdropout voltage is required for the LDO to function properly.

Herein we describe a high-efficiency converter system that is capable ofproducing multiple independently regulated output voltages and/orcurrents using a single converter without the addition of a tappedmagnetic structure, or LDO post-regulation stages. In the proposedconverter system, multiple outputs may be obtained when the singleconverter core is employed on a time-share basis. This allows a singlepower stage to alternately connect to any one of the loads to affectregulation as needed. In most cases, this may require a very highbandwidth power stage, precluding the approach for SMPS systemsoperating at typical switching frequencies (1 MHz and below). VHF powerconverters, such as those described herein may have the necessarybandwidth allowing many outputs to be serviced with high bandwidth.

FIG. 27 shows a VHF power converter implementation with multipletime-shared outputs implemented as described herein. The converter maybe a high-bandwidth converter that alternately supplies energy to aplurality of loads according to a schedule imposed by a control system.The converter system may be capable of supplying the total average powerdelivered to each load as well as the peak power required of any givenload over the course of a modulation cycle. It may also operate over theoutput voltage range set by the difference between the minimum andmaximum output voltages.

In one method of control, a controller may simultaneously monitors eachload (V1, V2, V3 . . . ) as depicted in FIG. 27. The converter is thenconnected through switches S1, S2, S3 . . . to each load over an evenfraction of the total modulation period TM equal to TM/N, where N is thenumber of loads. When any individual load is connected to the convertercell (a period henceforth referred to as a load window), the convertermay operate such that the average output voltage or current over TM ismaintained at the desired value according to a reference value that maybe accessible to the controller. This may be achieved by varying theon-off modulation duty ratio of the converter cell during the loadwindow. As the load demands more power, the duty ratio may be increasedand vice versa. The controller cycles through all the load windows inthe period TM, therefore no load remains unregulated for a period longerthan TM−TM/N. Since TM can be short with a high performance power stage,the effective regulation bandwidth can be very high.

This method of regulation may be achieved when the power stage iscapable of a peak output equal to N times the highest average loadpower. This derives because the converter cell may only deliver power toa load for 1/N of the modulation period, TM. When a constant output isdesired, the load capacitors shown in parallel with the load V1, V2 arepreferably sized to sustain the output during at least the period(N−1)TM/N.

Another method of control relaxes the requirements on the converter andfilters. In this method, the load window periods may be dynamicallyscaled according to the average output power of each load. This maypermit the converter to spend more time supplying power to larger loadswhile reducing the peak power required of the converter for a givenaverage load power. One such method is to scale the load window periodin direct proportion to the average power demanded from the load. Thiswill give longer windows to higher loads. In steady stage this maycorrespond to requiring minimum peak converter power. The load windowscaling period may be adjusted at a frequency well below the cutoff of acontrol loop frequency of the converter. However, in certain cases itwill be advantageous to make the load window period nearly equal to orequal to the duty ratio of the converter with respect to the load.

For the converter depicted in FIG. 27, the operation when supplyingthree loads with different output voltages is described subsequently.Each output is assumed to be a unique value for the purpose ofillustration, though all could be identical in practice.

The modulation period is divided into three distinct periods defined bywhich load is connected to the converter's output. Each of these periodsis a load window, occurring when the respective load switch (S1-3) isclosed and the others remain open. For this particular example, the loadwindows are of constant length and active sequentially.

During operation, a master controller continually monitors the outputvoltage of each load. When a load window becomes active, the converteroutput voltage may quickly rise (or fall) to close to the load voltagerequired. The converter may then be operated for a fraction of the loadwindow period, such that the output voltage is maintained withinpre-specified limits over the entire modulation period. The fraction ofthe load window period may range from 0 to 1 and may be determined in anaverage sense by the controller. In one example control scheme, eachload is controlled by an independent window loop where the fraction ofthe window would correspond to a duty ratio similar to a standard PWMcontrol scheme. A primary difference being that the fraction relates tothe actual converter on-time, such as by a scale factor of TW/TM.

When the master controller asserts the “next” window, control of theconverter is based on a “next” window loop. The converter output mayimmediately slew to the “next” output voltage. The converter may then beoperated with the appropriate duty ratio as described above. This cyclemay repeat continuously as the master control loop sequentially shiftsthe active window.

Owing to the very small energy storage inherent in a VHF power stage,the output voltage slew time at the start of each new load window may bevery short. As a result, it has substantially no effect on the controlsystem in an average sense. Instead, control may be dominated by theload-output capacitor time constant, and the window-window modulationdelay. This may allow standard PWM schemes to be directly compatible.Many other control schemes are possible where the converter output istime-shared across multiple loads. These include hysteretic, averagecurrent mode control, and PWM with hysteretic override.

A primary benefit of this scheme is the ability to simplify the overallconverter architecture while achieving multiple fully-regulated outputs.This derives from the time-sharing aspect of this technique as enabledby a high-bandwidth VHF converter as described herein.

One application of particular interest is for control of multiple LEDstrings to affect color shifting and modulation of overall brightness.In this case, the converter may operate as a current regulator. Eachstring may be one load. As the converter cycles through each loadwindow, the output current may be regulated to the desired value and thepower stage may naturally obtain the desired string voltage veryrapidly. Since the current to each stage can be independently regulatedusing this scheme, color shifting may be readily achieved. A mastercontrol loop may set the current for each string such that the colortemperature and brightness may be simultaneously satisfied.

Since the AC/DC VHF converter stages described herein may also have veryhigh control bandwidth, a VHF AC/DC converter may be readily controlledin this manner. The result is a converter system that achievesindependent regulation of multiple output strings in a single stage.This compares favorably with existing technology that requires aseparate AC/DC stage to provide a regulated DC rail followed by adedicated set of controllers that are DC/DC converters to match thevoltages required by each string. For the LED case, in particular, itmay not be necessary to use hold-up capacitors at the output because themodulation frequency can be maintained very far above the persistence ofvision limits of the human eye.

Another application of particular interest is in portable electronicsthat require multiple output voltages, for example, the cell phone. Inthis case, each output is buffered by a capacitor that is sized tosustain the output during the interval when the converter is servicingother loads. Allowing for dynamic windowing in this case can minimizethe load capacitor sizes. The total system size may be reducedregardless, because multiple power stages may be replaced by a singlecontrollable stage that may have equivalent or greater power density.

A VHF power converter architecture as described herein may operate withvery high efficiency. Efficiencies of 70% or greater can be delivered bya VHF soft-switched power converter through modest control optimization.Although higher efficiencies may be desirable in limited applications,the VHF power converter architecture described herein may operate atefficiencies of 90% or greater with control optimized for efficiency.

Very high efficiency may also ameliorate a demand that is often animportant consideration in switch mode power supply integration—heatbuild up from efficiency loss. The result may be a very highly efficientconverter that produces less heat energy per unit volume (power density)than conventional converters for a given output power requirement. At50% efficiency, a SMPS must dissipate half of the energy that itconsumes from an input as heat. Whereas an 80% efficient VHF powerconverter based on the soft-switched cell technology and the likedescribed herein need only be concerned with dissipating twenty percentof power consumed as heat.

VHF power converter size may be influenced by the component technologyrequired; therefore faster switching rates generally enable smallerdevices. Key component size considerations include inductors andcapacitors. By reducing the amount and quality of stored energy, thehigh efficiency, soft-switching VHF converters described herein may besuccessfully and economically implemented with small value (andtherefore small size) inductors and capacitors. While these twocomponents are not the only beneficiaries of the architecture and switchcontrol techniques described herein, they are generally significant sizefactors. By enabling use of air-core printed circuit board etch-basedinductors and/or transformers with or without magnetic core material,physical device size is essentially moot. The stacked cell highefficiency, soft-switched VHF power converter architectures describedherein may be applied in an LED driver application without requiringinductors greater than one micro-henry. Likewise a switching AC to DCpower converter based on the cell-based architectures described hereinmay be implemented with no inductors larger than five micro-henry.

Such a small form factor device may be implemented as a stacked cellserial input, parallel out high efficiency fully resonant switching VHFAC to DC power converter further including synchronous rectification atthe output. Other features and/or benefits from using a VHF converter insuch a small form factor device may include built in FCC emissionsfiltering, lightning strike protection, a diode-based input rectifier,no need for electrolytic capacitors, VHF operation frequency, little orno DC energy storage while providing substantially pure DC output froman AC source, capable of driving an LED with no visible light flicker,substantially no output ripple, substantially no 2F line frequency beingpropagated to the output, and the like. A small form factor VHFconverter may further include generating an output voltage that isindependent of instantaneous input voltage to allow for deliveringsubstantially constant output power throughout an AC line cycle.

By enabling the use of ceramic surface mount capacitors and printedcircuit board etched inductors (rather than discrete inductors and/orlarge capacitors) a VHF power converter shape may result in asubstantially planar form. Such a form can readily be integrated intosmall spaces such as laptop display screens, mobile phones, and thelike.

The size benefits of a VHF cell-based power converter as describedherein may facilitate providing an AC to DC high isolation converter ina volume less than five US quarter dollar coins (approx. 4,050 cubicmillimeters). Other features that may be provided in this small volumemay include providing substantially ripple free (arbitrarily smallripple) output, ultra-high efficiency (e.g. greater than 75%), and thelike. In a volume of approximately three US quarter dollar coins(approx. 2,430 cubic millimeters), the VHF conversion techniques andarchitecture described herein may provide a very high power 50 W capableVHF power converter (e.g. for a laptop computer). Alternatively anultra-small 15 W capable VHF power converter (e.g. for driving an LED)may be provided in a volume smaller than one US quarter dollar coin(approx. 800 cubic millimeters).

LED lighting may be controlled/powered by the inventive VHF convertercell-based architecture described herein. Referring to FIG. 28, acircuit for replacing an incandescent bulb with a multiple LED light2802 is compared to an LED driver 2804 based on the VHF convertertechniques and architecture described herein. Not only is size of theconverter substantially reduced, but the space that was previouslyoccupied by the LED driver 2802 can be used for heat sinking/cooling theLEDs thereby enabling much higher potential light output from the samesize package (e.g. an A19 style bulb).

LED lighting controllers that may be possible with the VHF cell-basedpower converter methods and systems described herein may include: an ACto DC VHF converter to pulse-width-modulate an LED; a VHF converter topulse-width-modulate an LED; a stacked VHF converter topulse-width-modulate an LED; an AC to DC VHF switching converter topower an LED; a VHF switching power converter to power an LED; a stackedcell VHF converter to power an LED; a power converter operating atgreater than 5 MHZ to drive an LED without use of an electrolyticcapacitor; cycling on/off a power conversion stage of the VHF converterto control an LED; using a conversion stage of the VHF converter as apulse-width-modulation mechanism; a stacked-cell series input, paralleloutput high efficiency soft-switching/fully resonant switching VHF LEDpower supply including PWM control of the LED with optional power factorcorrection.

The VHF power converter of the present invention may be used in laptoppower supplies, mobile phones, sports equipment, household appliances,LED-based lights, wireless base stations, electric vehicles, radarsystems, soldier-carried military field equipment and the like. The VHFpower converter described herein may be used with any application wherea higher voltage, such as 12V may need to be converted to a lowervoltage, such as 3V to power digital electronics and the like. Theinventive VHF power converter may have fast transient response and maybe configured to accept a very wide range of inputs such as from 12VDirect Current (DC) to 240 V Alternating Current (AC). Note that thevoltage references here are merely exemplary and different voltages andcurrent types (e.g. 15 VAC input, 12V output) may be used and/orprovided by the VHF converter. Further, the methods and systems of a VHFpower converter described herein may provide significant size benefitsto product designers by enabling configuration of a very small sizedpower source for use with electronic devices.

Examples of an electronic device that may receive DC power from theinventive VHF power converter or other power circuit may include ahandheld computer, a miniature or wearable device, a portable computer,a desktop computer, a router, an access point, a backup storage devicewith wireless communications capabilities, a mobile telephone, a musicplayer, a remote control, a global positioning system device, a devicethat combines the functions of one or more of these devices, and thelike.

A laptop may present several opportunities for use of the VHF converterincluding converting may DC motherboard power to provide various DCvoltages as is sometimes needed for operating a processor, bus logic,peripherals, display backlight and the like. Not only are thesesupplemental power needs met by the inventive VHF converter, but themain power converter from AC line (e.g. to charge the laptop battery)may be provided. The small size of the power converter may require lessspace than other contemporary solutions. For example, the main AC to DCpower supply, that is typically found in-line with the line cord may bemade substantially smaller or even eliminated because the VHF powerconverter may be put inside the laptop or battery enclosure.

Another laptop application is to use the inventive VHF power converteras a source of power for the display (e.g. for a display backlight).This may benefit the quality of the display because the fast transientresponse offered by the VHF power converter may provide improved displayquality, brightness, sharpness, and the like. In addition, the VHF powerconverter small size requirement may allow it to be built into thedisplay housing (e.g. the laptop fold-up top cover) thereby reducingassembly complexity of the laptop system.

As mentioned herein, the power converter may receive a wide range ofinputs for powering low voltage systems mentioned herein and furtherincluding devices such as portable radios, two-way radios, televisions,audio equipment, wearable microphones, headsets, virtual realityeyewear, augmented reality headgear, and the like. In addition to thesemostly portable devices, other small devices that may be powered fromthe AC line such as a mobile phone charger, a battery charger, and thelike may benefit from application of the inventive VHF converterdescribed herein. Other AC line applications include, without limitationcharging a palmtop, a smart phone, a Global Positioning System (GPS)system, electric razor, and the like. In embodiments, the powerconverter of the present invention may be used for powering devices thatrange in power from a high-power laptop to a low-power cell phone.

Further, the power converter may be used in wireless security monitoringsystem, energy saving lamps and other household appliances. The powerconverter may convert standard AC voltage supply in houses to DCvoltages required in wireless security monitoring system, energy savinglamps and other household appliances. The inventive VHF power convertermay accept a very wide range of inputs, and hence, it can be employed indifferent household appliances requiring different voltages. Further,the small size requirement of the VHF power converter may allow it to bebuilt into any household appliance.

The VHF power converter may be used for sports equipment, such as ahelmet camera. A helmet camera may also require a variety of voltages,for powering the memory, image sensor, lighting, radio, and the like. Anembodiment of the VHF power converter may convert a DC voltage that maybe supplied from a battery (e.g. 18V) various DC voltages required inthe operation of the helmet camera. By applying the multi-channelcapabilities described herein, each load (lighting, sensor, radio, etc)that requires a different voltage or current for proper operation can beserviced by a single multi-channel converter described herein. Further,because of its small size, the VHF power converter may fit easily intothe helmet camera housing and may be readily integrated into a printedcircuit board that may include the logic and functional elements poweredby the converter.

The inventive VHF power converter may be integrated into a displayscreen module to provide power for backlighting the display of a laptopor the like. This may benefit the quality of the display because thefast transient response offered by the VHF power converter may provideimproved display quality, brightness, sharpness, and the like. Inaddition, the small size requirement of the VHF power converter mayallow it to be built into the display screen module housing, therebyreducing assembly complexity of the display screen module.

The inventive VHF power converter may be integrated into an AC powercord. As mentioned earlier, the inventive VHF power converter mayreceive a wide range of power inputs. Hence, the AC power cord havingthe inventive VHF power converter may be connected to nearly any type ofpower source (e.g. AC line cord, 12V car charger, and the like). In atypical application, line AC power may be converted to low voltages thatmeet low-voltage safety requirements (e.g. less than 30V). The smallsize of the power converter may require less space than othercontemporary solutions so that a typical 50 W line cord power convertermay be disposed in an enclosure no larger than five U.S. quarter dollarcoins (approx. 4050 cubic mm).

Mobile phone applications of the VHF power converter include providingthe main electronics power from a battery, dedicated power for thephone's display including a backlit display, keypad back lighting,camera flash lamp, and the like. The high degree of integration affordedby the inventive VHF power converter described herein and the simplifiedPCB-based embedded inductor functionality with which the VHF powerconverter is compatible may afford direct integration on the mainelectronics printed circuit board.

The inventive VHF power converter may also be used in LED-basedlighting. LED lighting products that are compatible with existingincandescent fixtures need to operate from standard AC line voltage. LEDlight bulbs include multiple diodes, which use direct current (DC). Theinventive VHF power converter may convert standard AC voltage to DCvoltage required by diodes in LED light bulbs. In addition, the smallsize requirement of the VHF power converter may allow it to be builtinto the base of an LED-based replacement light bulb, thereby reducingassembly complexity of the LED light bulbs and providing a substantialamount of the interior of the bulb for heat sinking the LEDs.

A multi-channel embodiment of the inventive VHF power converter may beused to power LED strings so that each light or group of lights can beindividually controlled for brightness, color, on/off (blink), and thelike by employing a separate output value (current or voltage) for eachlight/group of lights. In addition, the inventive VHF power convertermay improve design and packaging of the LED strings owing to its smallsize.

The inventive VHF power converter may also be used in color changingLEDs. The inventive VHF power converter may provide color lightintensity control. The inventive VHF power converter may further providecolor point maintenance against LED junction temperature change, andlimiting LED device temperature to prolong LED lifetime.

The inventive VHF power converter may also be used in a wireless basestation. The inventive VHF power converter may convert an input voltageto an output voltage or current required by the wireless base stationtransceiver. The inventive VHF power converter may benefit low power RFapplications through its fast transient response time, RF envelopetracking output, and small size.

The VHF converter may find varied applications in vehicle-basedelectronics. In an embodiment, the power converter may be used forpowering vehicle accessories such as cell phone chargers, GPS Systems,mp3 players, stereo system, and the like that may plug into a 12 VDCvehicle power port. The inventive VHF power converter may provide powerto display units of GPS systems. This may result in improved displayquality, brightness, sharpness, and the like because of the fasttransient response offered by the VHF power converter. In addition, thesmall size requirement of the VHF power converter may allow it to bebuilt into the display unit, thereby reducing assembly complexity of theGPS system. Owing to the small size, the inventive VHF power convertermay be integrated into the cell phone chargers, GPS Systems, mp3players, and stereo systems in vehicles.

The inventive VHF power converter may also be used in airborne radar.Airborne radar presents unique design challenges, mainly in theinstallation constraints on the size of the airborne radar. Theinventive VHF power converter small size requirement may allow it to bebuilt into the airborne radar, thereby solving installation constraintsof the airborne radar. Radar systems may further benefit from the fasttransient response ability of the VHF power converter and wide range ofoutput voltage capability, extremely low ripple, high isolation, and thelike.

The inventive VHF power converter may also be used in Soldier-carriedmilitary field equipment. The inventive VHF power converter may convertan input signal to an output signal (e.g. voltage), as per requirementof a military field equipment, and aid in efficient power management.The military field equipment may include night-vision goggles, laptops,and communication devices such as GPS, sensors, and the like. The smallsize requirement of the VHF power converter may allow it to be builtinto the military field equipment, thereby making the military fieldequipment lightweight, reliable, and portable. In addition, theinventive VHF power converter may provide military equipment designerswith a single power converter design that is able to adapt to the powerneeds of all sorts of military field equipment.

The inventive VHF converter methods and systems described herein may becombined with varactor-based network tuning to support a very large loadrange. Such a combination may take advantage of varactor control ofresonance and VHF on/off switching to facilitate compensation forimpedance changes as a function of load.

What is claimed is:
 1. A power converter, comprising: an inverter stagefor receiving an input and generating an inverter output, wherein theinverter stage comprises an inverter switch configured to switch theinverter stage; a synchronous rectifier stage for receiving the inverteroutput and for delivering an output of the power converter to a load,wherein the synchronous rectifier stage comprises a synchronousrectifier switch configured to switch the synchronous rectifier stage; acontroller configured to control the output of the power converter bymodulating at least one of the inverter stage and the synchronousrectifier stage on and off at a frequency less than a switchingfrequency of the at least one of the inverter stage and the synchronousrectifier stage, the controller being further configured to adjust,independently of an amount of power delivered to the load, one or moreof a duty cycle of the inverter switch, a duty cycle of the synchronousrectifier switch, and a phase between switching of the inverter switchand switching of the synchronous rectifier switch; and at least onecomponent connected between the inverter stage and the synchronousrectifier stage.
 2. The power converter of claim 1, wherein thecontroller is further configured to control switching of at least one ofthe inverter switch and the synchronous rectifier switch based on atleast one of an efficiency of the power converter and achieving a chosenwaveform shape.
 3. The power converter of claim 1, wherein thecontroller is further configured to use feedback combined with themodulating to control at least one of the input of the inverter stageand an output power provided by the output of the power converter. 4.The power converter of claim 2, wherein the controller is furtherconfigured to switch the at least one of the inverter switch and thesynchronous rectifier switch independently of control of the output ofthe power converter.
 5. The power converter of claim 1, wherein thecontroller is further configured to control the output of the powerconverter by modulating the power converter on and off at a frequencyless than a switching frequency of at least one of the inverter stageand the synchronous rectifier stage, wherein the power converter isconfigured to control one or more of the duty cycle of the inverterswitch, the duty cycle of the synchronous rectifier switch, and thephase between the switching of the inverter switch and the synchronousrectifier switch based on an efficiency of the power converter and/orbased on achieving a chosen waveform shape.
 6. The power converter ofclaim 1, wherein the controller is further configured to control theswitching of the at least one of the inverter switch and the synchronousrectifier switch by at least one switching function parameter that isbased on at least one of the following port parameters: an inverter portvoltage, an inverter port current, a synchronous rectifier port voltage,and a synchronous rectifier port current.
 7. The power converter ofclaim 1, wherein the inverter switch is controlled as a function of atleast one of the following: an inverter port voltage, an inverter portcurrent, a synchronous rectifier port voltage, and a synchronousrectifier port current.
 8. The power converter of claim 1, wherein thesynchronous rectifier switch is controlled as a function of at least oneof the following: an inverter port voltage, an inverter port current, asynchronous rectifier port voltage, and a synchronous rectifier portcurrent.
 9. The power converter of claim 1, wherein the inverter switchis controlled as a function of an average of at least one of thefollowing: an inverter port voltage, an inverter port current, asynchronous rectifier port voltage, and a synchronous rectifier portcurrent.
 10. The power converter of claim 1, wherein the synchronousrectifier switch is controlled as a function of an average of at leastone of the following: an inverter port voltage, an inverter portcurrent, a synchronous rectifier port voltage, and a synchronousrectifier port current.
 11. The power converter of claim 1, wherein thecontroller is configured to control switching of at least one of theinverter switch and the synchronous rectifier switch based on parametersof an inverter port and a synchronous rectifier port.
 12. The powerconverter of claim 1, wherein the controller is configured to controlswitching of at least one of the inverter switch and the synchronousrectifier switch to achieve zero-voltage switching (ZVS) or near-ZVS.13. The power converter of claim 1, wherein the power convertercomprises a plurality of power converter cells, wherein the powerconverter cells are connected in at least one of series and parallel toprovide a combined power converter output for delivery to the load,wherein the inverter stage comprises an inverter stage of at least oneof the power converter cells, and wherein the synchronous rectifierstage comprises a synchronous rectifier stage of at least one of thepower converter cells.
 14. The power converter of claim 1, wherein theinverter stage is configured as at least one of the following inverterclasses: Class-Φ2, and Class-E.
 15. The power converter of claim 1,wherein the synchronous rectifier stage is configured as at least one ofthe following synchronous rectifier classes: Class-Φ2, and Class-E. 16.The power converter of claim 1, wherein the controller is configured tocontrol at least one of a phase and a duty cycle of the one or more ofthe inverter switch and the synchronous rectifier switch using atransfer function that is based on at least one of the following: aclosed-form mathematical solution, a numerical simulation, and directmeasurement.
 17. The power converter of claim 1, wherein the inverterstage is configured to receive a substantially DC input.
 18. The powerconverter of claim 1, wherein the synchronous rectifier stage isconfigured to deliver to the load a substantially DC output.
 19. Thepower converter of claim 1, wherein the controller is configured tocontrol, independently of an amount of power delivered to the load, theduty cycle of the inverter switch.
 20. The power converter of claim 1,wherein the controller is configured to control, independently of anamount of power delivered to the load, the duty cycle of the synchronousrectifier switch.
 21. The power converter of claim 1, wherein thecontroller is configured to control, independently of an amount of powerdelivered to the load, the phase between the switching of the inverterswitch and the switching of the synchronous rectifier switch.
 22. Thepower converter of claim 1, wherein the controller is further configuredto: choose a level of converter performance, wherein the chosen level ofconverter performance comprises at least one of a chosen level ofefficiency and a chosen waveform shape; and implement at least onetransfer function that will result in the chosen level of performance,wherein the at least one transfer function comprises a function of atleast one of an inverter stage input voltage and a synchronous rectifierstage output voltage, and wherein the implementing comprises measuringthe at least one of the inverter stage input voltage and the synchronousrectifier stage output voltage, applying the at least one of theinverter stage input voltage and the synchronous rectifier stage outputvoltage to the at least one transfer function, and adjusting switchingparameters of at least one of the inverter switch and the synchronousrectifier switch based on the at least one transfer function.
 23. Thepower converter of claim 22, wherein the at least one transfer functioncomprises at least one of the following: a first transfer function forthe duty cycle of the inverter switch, a second transfer function forthe duty cycle of the synchronous rectifier switch; and a third transferfunction for the phase between the switching of the inverter switch andthe synchronous rectifier switch; and wherein the implementing furthercomprises adjusting at least one of the duty cycle of the inverterswitch, the duty cycle of the synchronous rectifier switch, and thephase between the switching of the inverter switch and the switching ofthe synchronous rectifier switch based on the at least one transferfunction.
 24. The power converter of claim 23, wherein the controller isfurther configured to control the switching of the at least one of theinverter switch and the synchronous rectifier switch by at least oneswitching function parameter that is based on at least one of thefollowing port parameters: an inverter port voltage, an inverter portcurrent, a synchronous rectifier port voltage, and a synchronousrectifier port current.
 25. The power converter of claim 22, wherein theat least one transfer function is based on at least one of thefollowing: a closed-form mathematical solution, a numerical simulation,and direct measurement.
 26. The power converter of claim 1, wherein thecontroller is configured to control an input of the power converter bymodulating at least one of the inverter stage and synchronous rectifierstage on and off at the frequency less than the switching frequency ofat least one of the inverter stage and the synchronous rectifier stage.27. The power converter of claim 1, wherein the power converter has aswitching frequency of at least 1 MHz.
 28. The power converter of claim1, wherein the inverter stage is a resonant inverter stage.
 29. Thepower converter of claim 1, wherein the rectifier stage is a resonantrectifier stage.
 30. The power converter of claim 1, wherein the atleast one component comprises a transformation network.
 31. A powerconverter, comprising: a resonant inverter stage for receiving an inputand generating an inverter output, wherein the resonant inverter stagecomprises an inverter switch configured to switch the resonant inverterstage; a synchronous rectifier stage for receiving the inverter outputand for delivering an output of the power converter to a load, whereinthe synchronous rectifier stage comprises a synchronous rectifier switchconfigured to switch the synchronous rectifier stage; and a controllerconfigured to control the output of the power converter by modulating atleast one of the resonant inverter stage and the synchronous rectifierstage on and off at a frequency less than a switching frequency of theat least one of the resonant inverter stage and the synchronousrectifier stage, the controller being further configured to adjust,independently of an amount of power delivered to the load, one or moreof a duty cycle of the inverter switch, a duty cycle of the synchronousrectifier switch, and a phase between switching of the inverter switchand switching of the synchronous rectifier switch.
 32. The powerconverter of claim 31, wherein the controller is further configured tocontrol switching of at least one of the inverter switch and thesynchronous rectifier switch based on at least one of an efficiency ofthe power converter and achieving a chosen waveform shape.
 33. A powerconverter, comprising: an inverter stage for receiving an input andgenerating an inverter output, wherein the inverter stage comprises aninverter switch configured to switch the inverter stage; a synchronousrectifier stage for receiving the inverter output and for delivering anoutput of the power converter to a load, wherein the synchronousrectifier stage comprises a synchronous rectifier switch configured toswitch the synchronous rectifier stage; and a controller configured tocontrol the output of the power converter by modulating at least one ofthe inverter stage and the synchronous rectifier stage on and off at afrequency less than a switching frequency of the at least one of theinverter stage and the synchronous rectifier stage, the controller beingfurther configured to adjust, independently of an amount of powerdelivered to the load, one or more of a duty cycle of the inverterswitch, a duty cycle of the synchronous rectifier switch, and a phasebetween switching of the inverter switch and switching of thesynchronous rectifier switch, wherein the power converter is configuredto switch at a switching frequency that exceeds 1 MHz.
 34. The powerconverter of claim 33, wherein the controller is further configured tocontrol switching of at least one of the inverter switch and thesynchronous rectifier switch based on at least one of an efficiency ofthe power converter and achieving a chosen waveform shape.